 Research Article
 Open Access
A Practical Scheme for Frequency Offset Estimation in MIMOOFDM Systems
 Michele Morelli^{1},
 Marco Moretti^{1}Email author and
 Giuseppe Imbarlina^{1}
https://doi.org/10.1155/2009/821819
© Michele Morelli et al. 2009
 Received: 27 June 2008
 Accepted: 25 December 2008
 Published: 28 January 2009
Abstract
This paper deals with trainingassisted carrier frequency offset (CFO) estimation in multipleinput multipleoutput (MIMO) orthogonal frequencydivision multiplexing (OFDM) systems. The exact maximum likelihood (ML) solution to this problem is computationally demanding as it involves a line search over the CFO uncertainty range. To reduce the system complexity, we divide the CFO into an integer part plus a fractional part and select the pilot subcarriers such that the training sequences have a repetitive structure in the time domain. In this way, the fractional CFO is efficiently computed through a correlationbased approach, while ML methods are employed to estimate the integer CFO. Simulations indicate that the proposed scheme is superior to the existing alternatives in terms of both estimation accuracy and processing load.
Keywords
 Training Sequence
 Carrier Frequency Offset
 Orthogonal Frequency Division Multiple Access
 MIMO Channel
 Pilot Symbol
1. Introduction
Orthogonal frequencydivision multiplexing (OFDM) is an attractive modulation technique for wideband wireless communications due to its robustness against multipath distortions and flexibility in allocating power and data rate over distinct subchannels. For these reasons, it is adopted in a variety of applications, including digital audio broadcasting (DAB), digital video broadcasting (DVB), and the IEEE 802.11a wireless local area network (WLAN) [1]. Combining OFDM with the multipleinput multipleoutput (MIMO) technology is an effective solution to increase the capacity of practical commercial systems. The deployment of multiple antennas at both the transmitter and receiver ends can be exploited to improve reliability by means of spacetime coding techniques and/or to increase the data rate through spatial multiplexing [2].
Similar to singleinput singleoutput (SISO) OFDM, MIMOOFDM is extremely sensitive to carrier frequency offsets (CFOs) induced by Doppler shifts and/or oscillator instabilities. The CFO destroys orthogonality among subcarriers and must be accurately estimated and compensated for to avoid severe error rate degradations [3]. While CFO recovery is a wellstudied problem for single antenna systems, only few solutions are available for MIMOOFDM. A blind kurtosisbased scheme is presented in [4], while a method for jointly estimating the CFO and MIMO channel is derived in [5] by placing null subcarriers and pilot tones across adjacent OFDM blocks. Unfortunately, these methods are quite complex as they require a largepoint discrete Fourier transform (DFT) operation and a computationally demanding line search. Furthermore, they provide the CFO estimate upon observation of several OFDM blocks, and accordingly, are not suited for packetoriented applications, where synchronization must be completed shortly after the reception of a packet. In order to achieve fast timing and frequency recovery, training sequences with a periodic structure are commonly employed in SISOOFDM systems [6–8]. Extending this approach to MIMOOFDM, however, is not straightforward as signals emitted from different antennas give rise to multistream interference (MSI) at the receiver station, which may degrade the accuracy of the synchronization algorithms. The detrimental effect of MSI can be alleviated by a careful design of the MIMO preambles. For instance, in [9], it is shown that the performance of the leastsquares (LSs) channel estimator is optimized if the training sequences at different TX branches are orthogonal and shiftorthogonal for at least the channel length. To meet such requirement, a timeorthogonal design is employed in [10], where different TX antennas transmit their preambles over disjoint time intervals. In this way, however, the preamble length grows linearly with the number of TX branches, thereby, increasing the system overhead. The use of chirplike polyphase sequences is suggested in [11], while a training block composed of repeated PN sequences with good crosscorrelation properties is employed in [12]. In both cases, the CFO estimate is obtained by crosscorrelating the repetitive parts of the received preambles in a way similar to SISOOFDM. This approach is also adopted in [13, 14], where the pilot sequences are obtained by repeating Chu or FrankZadoff codes with a different cyclic shift applied at each TX antenna. Alternative criteria for MIMOOFDM preamble design can be found in [15, 16].
A subspacebased method for CFO estimation in MIMOOFDM has recently been proposed in [17]. In this scheme, pilot symbols at different transmit antennas are frequencydivision multiplexed (FDM) and placed over equally spaced subcarriers. The resulting preambles are characterized by an inherent periodic structure in the time domain which can be effectively exploited at the receiver to separate signals arriving from different TX antennas. This approach is reminiscent of the multiplesignalclassification (MUSIC)based frequency recovery scheme employed in [18] in the context of orthogonal frequency division multiple access (OFDMA). The main advantage with respect to [18] is that in [17], the CFO estimate is obtained with reduced complexity by looking for the roots of a realvalued polynomial function. A rootbased approach is also adopted in [19] after writing the CFO metric in polynomial form.
In this paper, the repetitive slotsbased CFO estimator discussed in [8] is extended to MIMOOFDM transmissions. In order to enlarge the frequency acquisition range, however, we decompose the CFO into a fractional part plus an integer part. The fractional CFO is computed first by crosscorrelating the repetitive segments of the received preambles in a way similar to [8], while the integer CFO is subsequently estimated by resorting to maximum likelihood (ML) methods. This results into an algorithm of affordable complexity which can estimate large CFOs and whose accuracy attains the relevant CramerRao bound (CRB).
The rest of this paper is organized as follows. Section 2 describes the system model and introduces basic notation. In Section 3, we review the joint ML estimation of the CFO and MIMO channel, while Section 4 is devoted to the training sequences design and CFO recovery scheme. Simulation results are presented in Section 5 and some conclusions are drawn in Section 6.
Notation 1. Matrices and vectors are denoted by boldface letters, with and being the DFT matrix and identity matrix of order , respectively. denotes an diagonal matrix with entries along its main diagonal, while is the inverse of a square matrix . We use , , , and for expectation, complex conjugation, transposition, and Hermitian transposition, respectively. The notation represents the Euclidean norm of the enclosed vector, while e , and stand for the real part, modulus, and principal argument of a complex number . Finally, denotes the ( )th entry of a matrix while is a trial value of the unknown parameter .
2. System Model
where is a power of two not smaller than , are integer parameters satisfying and are pilot symbols with constant modulus . In this way, the total energy allocated to training amounts to and is equally split between the TX antennas.
3. Maximum Likelihood Frequency Estimation
In the sequel, we refer to (7) as the maximum likelihood frequency estimator (MLFE). The following remarks are in order.
 (1)Observing that with rank and rank , it turns out that rank . Since has dimensions , a necessary condition for the existence of in the righthandside of (9) is that . On the other hand, from (4), it follows that has entries
 (2)By invoking the asymptotic efficiency property of the MLFE, the frequency estimate (7) is expected to be unbiased with an accuracy that approaches the corresponding CRB for large data records and sufficiently high signaltonoise ratios (SNRs). Using the LLF in (5), it is found that [19]:
4. Frequency Estimation with Reduced Complexity
4.1. Problem Formulation
 (C1)
pilot symbols are equipowered, equispaced in the frequency domain and modulate distinct subcarriers at different TX antennas according to the FDM principle;
 (C2)
each vector ??( ) of time domain samples is obtained by the repetition of identical segments, where is some power of two.
Condition C1 implies that the preambles remain shiftorthogonal in the time domain, which is desirable to enhance the accuracy of the channel estimates, while condition C2 facilitates CFO recovery by ensuring that the preambles are periodic with period .
where we set to ensure that the total energy allocated to training is still . It is worth observing that the use of timerepetitive FDM training sequences for MIMOOFDM has also been suggested in [16] to make the CRB of the frequency estimates independent of the channel realization. However, our design (14) is more general as it applies to any triple whereas in [16], the number of subcarriers is constrained to be a multiple of . Recalling that in practical OFDM systems is always a power of two, it turns out that the sequence design in [16] can only be adopted on condition that both and are powers of two.
while are statistically independent Gaussian vectors with zeromean and covariance matrix .
4.2. Estimation of the Fractional CFO
4.3. Estimation of the Integer CFO
If the normalized CFO is guaranteed to be less than in magnitude, the quantity can be regarded as an estimate of . Otherwise, is expressed as in (15), and an estimate of the integer offset must be found. This problem is now addressed using ML methods.
In the sequel, we refer to (35) as the reduced complexity frequency estimator (RCFE).
4.4. Remarks
(1) As mentioned previously, matrix in (28) is nonsingular provided that . Such condition is more restrictive than the constraint that was found in the previous section for MLFE. In particular, recalling that , it turns out that the maximum channel length that RCFE can manage is times smaller than for MLFE.
(3) The computational load of RCFE can be assessed as follows. Computing the correlations in (19) requires a total of real operations (additions plus multiplications) for each RX branch, while operations are needed to obtain in (23). Quantities in (33) are computed through an point DFT for each receiving antenna, with a corresponding complexity of . Finally, evaluating in (34) needs additional operations for each . The overall complexity of RCFE is summarized in the first row of Table 1, where a distinction has been made between the FCFO and ICFO recovery tasks, and we have denoted by the number of hypothesized ICFO values.
Complexity of FCFO and ICFO estimation schemes .
FCFO recovery  ICFO recovery  

RCFE 


PBFE 


CBFE 

Comparing this results with (38), we see that the loss (in dB) with respect to RCFE is Log , which approaches 1.25 dB for large values of . Furthermore, since no ICFO estimation is attempted in [12], the estimation range of CBFE is restricted to , while RCFE can cope with CFOs as large as . The overall complexity of CBFE is shown in the third line of Table 1. Compared to FCFO recovery by means of RCFE, the computational saving of CBFE is in the order of .
5. Simulation Results
Computer simulations have been run to check and extend the analytical results of the previous sections. The simulation scenario is summarized as follows.
5.1. Simulation Model
In (41), the constant is chosen such that the channel power is normalized to unity, that is, . A new channel snapshot is generated at each simulation run and kept fixed over the training period. Vectors are assumed to be statistically independent for different TX/RX antenna pairs. The training sequences employed by RCFE are given in (14), where we have set and . In this way, each TX antenna transmits a total of 32 pilot symbols which are randomly taken from a QPSK constellation with power . Parameters and are varied throughout simulations to assess their impact on the system performance.
over the set , with being the point DFT of . After ICFO compensation, the fractional CFO is eventually estimated by looking for the roots of a realvalued polynomial function that is obtained by applying the MUSIC principle. As mentioned in [17], the estimation range of PBFE is . Its computational requirement is mainly ascribed to the need for evaluating the correlation matrix of the received time domain samples and is summarized in the second row of Table 1.
5.2. Performance Assessment
6. Conclusions
We have addressed the problem of trainingassisted CFO recovery in MIMOOFDM systems. To reduce the computational burden required by the exact ML solution, we have divided the CFO into a fractional part plus an integer part and have designed FDM pilot sequences that are periodic in the time domain. The fractional CFO is estimated in closed form by measuring the phase rotations between the repetitive parts of the received preambles, while the integer CFO is estimated in a joint fashion with the MIMO channel matrix by resorting to the ML principle. The proposed scheme has affordable complexity and exhibits improved performance with respect to existing alternatives. For these reasons, we believe that it provides an effective approach for frequency synchronization in beyond third generation (3G) wideband MIMOOFDM transmissions.
Authors’ Affiliations
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