- Research
- Open Access

# Low complexity and high accuracy angle of arrival estimation using eigenvalue decomposition with extension to 2D AOA and power estimation

- Saleh O Al-Jazzar
^{1}Email author, - Artem Muchkaev
^{2}, - Ahmad Al-Nimrat
^{3}and - Mahmoud Smadi
^{3}

**2011**:123

https://doi.org/10.1186/1687-1499-2011-123

© Al-Jazzar et al; licensee Springer. 2011

**Received:**9 July 2011**Accepted:**7 October 2011**Published:**7 October 2011

## Abstract

In this paper, an angle of arrival (AOA) estimator is presented. Accurate AOA estimation is very crucial for many applications such as wireless positioning and signal enhancement using space processing techniques. The proposed estimator is based upon applying the eigenvalue decomposition (EVD) method on the crosscorrelation matrix of the received signals at two sides of the antenna array doublets. The proposed method is named the eigenvalue-decomposition-based AOA (EDBA) estimator. In comparison with the ESPRIT algorithm, the EDBA has less complexity because the decomposition in the EDBA method is performed only once and on a smaller matrix dimension than that in the ESPRIT algorithm where the decomposition is performed twice. The other advantage is that the EDBA method has better performance than the ESPRIT algorithm. The EDBA is also extended to two-dimensional (2D) AOA estimation with automatic pairing in two ways. The first one performs the 2D AOA estimation by considering the eigenvalues of the crosscorrelation matrix to estimate the azimuth angles and their corresponding eigenvectors to estimate their corresponding elevation angles. Thus, the 2D AOA estimation is performed with automatic pairing and without the need for any pairing or searching techniques. The first 2D extension of the EDBA is named the EDBA-2D estimator. Another 2D AOA estimator that is based upon the EDBA method is also presented and named the Two-EDBA estimator. This second 2D estimator performs the pairing between the azimuth and elevation angles using the alignment of the eigenvalues' magnitudes. An additional advantage for the EDBA estimator is the fact that it provides an estimate for the received signal power paired automatically with its corresponding AOA estimate. Simulations of the proposed EDBA method and its 2D extensions with the signals' power estimation are shown to assess their performance.

## Keywords

- Antenna Array
- Additive White Gaussian Noise
- Elevation Angle
- Antenna Element
- Receive Signal Power

## 1 Introduction

Many applications require accurate estimation of the angle of arrival (AOA) of the received signal. Examples of these applications are signal reception enhancement [1, 2] and accurate wireless positioning [3, 4]. Many effects cause errors in the AOA estimation. An error in the AOA estimate can cause huge error when locating wireless devices or an increase in the bit error rate when detecting the received signal. Thus, it is of interest to develop techniques to estimate the AOA accurately.

In some cases, it is required to estimate two-dimensional (2D) angles, i.e., the azimuth and elevation angles. Besides the accuracy requirement for estimating both the azimuth and elevation angles, it is of interest to pair them for each of their corresponding source. The complexity of the estimator is another issue that requires the designers of the estimator to take care of. Also, in 2D AOA estimation, the antenna array geometry plays an important role in the estimation procedure. In this paper, we will assume two antenna array geometries and we will provide a 2D estimator, based upon the proposed estimator, for each of these geometries. The first one is the rectangular antenna array shape formulated from two-parallel uniform linear arrays (ULAs). The second antenna array geometry considered in this paper is the *L*-shaped antenna array formulated from two perpendicular ULAs.

ESPRIT or ESPRIT-based algorithms are proposed in the literature to perform the 2D AOA estimation, such as in [5–8]. Also, another method proposed to perform the pairing procedure is the modified propagator method (PM) [9, 10]. Although these methods do not require complex searching techniques as in [11–14], they still require pairing techniques in matching the angles estimated. The 2D AOA estimator proposed in [15] uses two-parallel ULAs, whereas the method in [16] is based upon matrix enhancement and the matrix pencil algorithm. The proposed method in [17] constructs a second-order statistic based upon the Schur-Hadamard product steering vector to perform the 2D AOA estimation. In [18], the authors propose an estimator that requires two ULAs to pair the azimuth and elevation angles. In [19–22], the authors propose 2D AOA techniques that apply singular value decomposition (SVD) on specially constructed covariance matrices.

In this paper, we propose an AOA estimator that enhances the AOA estimation with low computational complexity. The proposed AOA estimator utilizes the eigenvalue decomposition (EVD) method and is named the eigenvalue decomposition-based AOA (EDBA) estimator. The EDBA applies the EVD on a crosscorrelation matrix constructed from both sides of the antenna array doublets.

The first advantage of the proposed EDBA method is its low complexity. In fact, it has lower computational complexity than that of the well-known ESPRIT algorithm due to the fact that the decomposition used in the EDBA method is applied only once and on a smaller matrix dimension than that in the ESPRIT algorithm where the decomposition is applied twice [23]. The second advantage of the proposed methods is its better performance in estimating the AOA than that of the ESPRIT algorithm. Another benefit for using the EDBA method is its ability to estimate the received signals' power with automatic pairing with their corresponding AOA estimates.

The EDBA is also extended for 2D AOA estimation in two ways. The first one is named the EDBA-2D method. In this extension, the azimuth and elevation angles are estimated and paired automatically. The EDBA-2D method starts by formulating a crosscorrelation matrix from the received signals at both sides of two-parallel ULAs. Then, the azimuth angles are estimated from the eigenvalues of the crosscorrelation matrix, and the elevation angles are estimated from the corresponding eigenvectors of the same crosscorrelation matrix. Thus, automatic pairing between the estimated azimuth and elevation angles is provided by the correspondence between the eigenvalues and the eigenvectors of the crosscorrelation matrix. The second way presented to extend the EDBA method for 2D AOA estimation uses the EDBA method twice and separately at the two ULAs of the *L*-shaped antenna array to estimate the azimuth and elevation angles. Then, we pair them with their corresponding sources using the alignment of the eigenvalues' magnitudes. This method is named the Two-EDBA estimator. The EDBA-2D and Two-EDBA methods have the advantage of not requiring any searching process as well as possessing the advantages of the EDBA method over the ESPRIT algorithm as discussed above.

The paper is organized as follows: Section 2 introduces the system model that forms the foundation for the EDBA estimator. The proposed EDBA estimator is explained in Section 3. Section 4 presents the 2D AOA system models. The proposed 2D extensions for the EDBA method are presented in Section 5. Estimating the received signals' power is presented in Section 6. The simulated performance of the EDBA estimator and its 2D extensions with the signals' power estimation are presented in Section 7. Finally, conclusions are shown in Section 8.

## 2 System model for the EDBA estimator

*M*uniform antenna doublets (i.e., 2

*M*total antenna elements) as shown in Figure 1. Each antenna doublet is formed of two antenna elements spaced by a distance

*d*. We assume a

*K*BPSK sources signals, ${\left\{{\stackrel{\u2323}{s}}_{k}\left(t\right)\right\}}_{k=1}^{K}$, impinging upon the antenna array. The signal ${\stackrel{\u2323}{s}}_{k}\left(t\right)$ is represented as ${\stackrel{\u2323}{s}}_{k}\left(t\right)={s}_{k}\left(t\right)cos\left(2\pi {f}_{c}t\right)=\Re \left\{{s}_{k}\left(t\right)exp\left(j2\pi {f}_{c}t\right)\right\}$ where

*f*

_{ c }is the carrier frequency and ${s}_{k}\left(t\right)={\sum}_{i}{\alpha}_{k}\left(i\right)g\left(t-iT\right)$,

*i*is an integer which represents the time index and

*s*

_{ k }(

*t*) is the complex low-pass equivalent of ${\stackrel{\u2323}{s}}_{k}\left(t\right)$,

*T*is the symbol period,

*α*

_{ k }(

*i*) =

*A*

_{ k }

*β*

_{ k }(

*i*) where

*β*

_{ k }(

*i*) ∈ (-1, + 1) which represents the symbol parity and

*A*

_{ k }is a positive constant which represents the amplitude of

*s*

_{ k }(

*t*) and

*g*(

*t*) is the (raised cosine) pulse shaping function with

where *n* is an integer so that *s*_{
k
}(*nT*) = *α*_{
k
}(*n*).

*h*). So, to start developing the received signal model, first consider the sampled received signal at the antenna elements (after the matched filter stage) that are located on the upper part of the antenna doublets from doublet #1 to doublet #M, shown in Figure 1, and denote it as

**r**

_{1}(

*i*):

with *λ* is the signal wavelength, *d*_{
d
} is the distance between consecutive antenna doublets, and *θ*_{
k
} is the AOA for the *k* th signal. In addition, **n**_{1}(*i*) is the noise vector added to the received signal at the antenna elements located at the upper part of the antenna doublets, which is additive white Gaussian noise (AWGN) and has a covariance matrix of *σ*^{2} **I**_{
M
} × _{
M
}, where **I**_{
M
} × _{
M
} is the *M* × *M* identity matrix. Finally, (.)^{
T
} represents the transpose operation.

*M*× 1) received signal vector can be written in a matrix form as

From now on, we will drop the term (*i*) from all terms for simplicity.

**r**

_{2}. Thus,

and **n**_{2} is an AWGN at the lower side of the antenna array doublets.

Now we showed the received signal model at the antenna arrays, and we will next propose the EDBA estimator.

## 3 Proposed eigenvalue-decomposition-based AOA (EDBA) estimator

**R**

_{21}) between

**r**

_{2}and

**r**

_{1}as follows

where *p*_{
k
} is the power of the *k* th received signal.

We use here the assumption that **n**_{1} and **n**_{2} are independent realizations of AWGN.

**R**

_{21}as follows

**Γ**

_{Z}is a diagonal matrix with its diagonal containing the eigenvalues of

**R**

_{21}, i.e.,

where the largest *K* values of the diagonal elements of **Γ**_{Z} correspond to the *K* sources which we will call *γ*_{1→K}≡ *γ*_{1} → *γ*_{
K
} . Each element of *γ*_{1→K}corresponds to one of the *K* sources.

**R**

_{21}shown in (10), and from the definition of

**R**

_{21}in (8), we have

where **T** is the appropriate matrix to change the basis vectors.

**Γ**

_{Z}is an

*M*×

*M*matrix, and

**Z**and

**P**

_{ s }are

*K*×

*K*diagonal matrices. Also, the nonzero diagonal elements of

**Γ**

_{Z}are only the first

*K*diagonal elements and then (13) can be written as

**T**should be

*M*×

*K*. Also, the lower (

*M*-

*K*) ×

*K*part of

**T**should be all zero elements, i.e.,

**ϒ**,

**P**

_{ s }, and

**Z**, we can deduce

**P**

_{ s }and

**Z**are diagonal as well. So, from (18), we can deduce that the matrix

**ϒ**is diagonal too, i.e.,

**U**is defined as

**u**

_{ k }is the

*k*th column eigenvector of

**R**

_{21}, and the

*K*columns of

**U**that correspond to the

*K*largest (which are also nonzero) eigenvalues of

**R**

_{21}will be given the notation $\stackrel{\u0304}{\mathbf{U}}$, i.e.,

*M*-

*K*) columns of

**U**in (12) are multiplied by the zero matrix in (17), then the eigenvector matrix $\left(\stackrel{\u0304}{\mathbf{U}}\right)$ and the matrix

**A**(θ) span the same signal subspace, and we have

where **Ω** = **ϒ**^{-1} and is a diagonal matrix (since **ϒ** is a diagonal matrix). Thus, each column of $\stackrel{\u0304}{\mathbf{U}}$ is a rotated scaled version of a corresponding column in **A**(θ).

**a**(

*θ*

_{ k }) which is one of the columns in

**A**(θ) (as shown in (5)) and defined in (3) and (4), we can deduce

*θ*

_{ k }as follows

**A**(θ) (from which

**a**(

*θ*

_{ k }) and consequently

*a*

_{ μ }(

*θ*

_{ k }) can be deduced) is not available at the receiver, still we could deduce the matrix $\stackrel{\u0304}{\mathbf{U}}$ from

**U**. Thus, looking back at (25) in which

*ζ*

_{ k }is expressed in terms the elements of

**a**(

*θ*

_{ k }), and because

**u**

_{ k }is a rotated scaled version of

**a**(

*θ*

_{ k }), then

*ζ*

_{ k }that is the average relative phase between two consecutive elements of

**a**(

*θ*

_{ k }) can be expressed in terms of two corresponding consecutive elements of

**u**

_{ k }as follows

where **u**_{
k
}*,*_{
μ
} is the *μ* th element of the vector **u**_{
k
}.

*θ*

_{ k }can be estimated as follows

The performance of the proposed method will be shown in the simulation section (Section 7). In comparison with the ESPRIT method, the EDBA uses the EVD on an *M* × *M* matrix as shown in (10), whereas in the ESPRIT method, the EVD will be applied on a 2*M* × 2*M* for the same system model assumed [23]. Also, the EVD in the EDBA is applied only once, whereas in the ESPRIT method, the EVD is applied twice for estimating the AOA as shown in [23]. Next, we will present the system models that will be used for the extension of the EDBA method for estimating the 2D AOA with automatic pairing.

## 4 System model for 2D AOA estimation

*L*-shaped antenna array illustrated in Figure 3. In the next subsections, we will provide more insight into the system models for the parallel ULA and the

*L*-shaped antenna array.

### 4.1 Parallel ULA

*M*antenna parallel doublets (i.e., 2

*M*total antenna elements) as shown in Figure 2. Each antenna doublet is formed of two antenna elements spaced by a distance

*d*. To start developing the received signal model, first consider the sampled received signal after the matched filter stage (

**r**

_{ A }) at the antenna elements that are located on the right-hand side of each antenna doublets, shown in Figure 2, which is represented as

with *λ* is the signal wavelength and *d*_{
d
} is the distance between consecutive antenna elements at each ULA. In addition, **n**_{
A
} is the noise vector added to the received signal at the antenna elements (from *m* = 1 → *M*) located along the right-hand side of each antenna doublet, which is AWGN and has a covariance matrix of *σ*^{2}**I**_{
M
} × _{
M
}.

*M*× 1) received signal vector can be written in matrix form as

**r**

_{ B }. Thus,

and **n**_{
B
} is an AWGN vector at the left-hand side of the antenna array doublets.

The next subsection will provide some insight into the *L*-shaped antenna array.

### 4.2 The *L*-shaped antenna array

*L*-shaped antenna array is formed of two perpendicular antenna arrays as shown in Figure 3. The sampled received signal (

**r**

_{ z }) at the antenna elements (after the matched filter stage) that are located in the

*z*-axis direction is represented as

where **n**_{
z
} is the AWGN noise vector with a covariance matrix of *σ*^{2}**I**_{
M
} × _{
M
}.

*m*= 1 to

*m*=

*M*, that are located in the

*x*-axis direction is given the notation

**r**

_{ x }and is represented as

**b**(

*ϕ*

_{ k }) = [

*b*

_{1}(

*ϕ*

_{ k }) ...

*b*

_{ M }(

*ϕ*

_{ k })]

^{ T }and

Likewise, **n**_{
x
} is the AWGN noise vector, and it also has a covariance matrix of *σ*^{2}**I**_{
M
} × _{
M
}.

*M*× 1) received signal vectors can be written in matrix form as

Thus, the received signal models for the different 2D antenna arrays structures are presented.

## 5 Extension of the EDBA for 2D AOA estimation

In this section, we will propose two methods for which the EDBA can be used to estimate the azimuth and elevation angles with automatic pairing. The first method is named the EDBA-2D method that is based upon the parallel antenna array structure illustrated in Figure 2. The second method is named the Two-EDBA method that is based upon the *L*-shaped antenna structure in Figure 3.

### 5.1 Proposed EDBA-2D estimator

**R**

_{ BA }) between

**r**

_{ B }and

**r**

_{ A }as follows

**R**

_{ BA }as follows

**R**

_{ BA }, i.e.,

where the largest *K* values of the diagonal elements of $\stackrel{\u0303}{\Gamma}$ correspond to the *K* sources which we will call ${\stackrel{\u0303}{\gamma}}_{1\to K}\equiv {\stackrel{\u0303}{\gamma}}_{1}\to {\stackrel{\u0303}{\gamma}}_{K}$. Each element of ${\stackrel{\u0303}{\gamma}}_{1\to K}$ corresponds to one of the *K* sources. Also, $\stackrel{\u0304}{\mathbf{U}}$ is the eigenvector matrix for **R**_{
BA
}.

**R**

_{ BA }shown in (38), and from the definition of

**R**

_{ BA }in (37), we see that

where $\stackrel{\u0303}{\mathbf{T}}$ is the appropriate matrix to change the basis vectors.

*M*×

*M*matrix and

**P**

_{ s }and

**Y**are

*K*×

*K*diagonal matrices. Also, the nonzero diagonal elements of $\stackrel{\u0303}{\Gamma}$ are only the first

*K*diagonal elements. Thus, (41) can be written as

*M*×

*K*. Also, the lower (

*M*-

*K*) ×

*K*part of $\stackrel{\u0303}{\Gamma}$ should be all zero elements, i.e.,

**P**

_{ s }, and

**Y**, we can deduce

**P**

_{ s }and

**Y**are diagonal as well. So, from (45), we can deduce that the matrix $\stackrel{\u0303}{\mathbf{T}}$ is diagonal too, i.e.,

*p*

_{ k }is a power variable, then both terms are not complex variables. Thus, looking at both sides of (47), then

*ϕ*

_{ k }) is implicated in ∠

*y*

_{ k }as can be deuced from (33). Thus, the azimuth angle can be estimated from the eigenvalue of

**R**

_{ BA }as follows

For the elevation angle (*θ*_{
k
}), it is estimated from the eigenvectors of **R**_{
BA
} in a similar way as discussed in the EDBA estimator explained in Section 3. We will not repeat the discussion and derivation again in this section but rather we will give the final procedure on how to estimate the elevation angle *θ*_{
k
}.

where ${\stackrel{\u0303}{\mathbf{u}}}_{k,\mu}$ is the *μ* th element of the vector ${\stackrel{\u0303}{\mathbf{u}}}_{k}$.

*θ*

_{ k }can be obtained as follows

Because of eigenvalue-eigenvector correspondence, estimation of the azimuth angle (*ϕ*_{
k
}) for the *k* th signal from the *k* th eigenvalue $\left({\stackrel{\u0303}{\gamma}}_{k}\right)$ and its corresponding elevation angle (*θ*_{
k
}) from the corresponding *k* th eigenvector $\left({\stackrel{\u0303}{\mathbf{u}}}_{k}\right)$ is performed with automatic pairing and without the need of any pairing procedure.

### 5.2 Proposed two-EDBA estimator

The Two-EDBA method is based upon the *L*-shaped antenna structure in Figure 3. The Two-EDBA starts by estimating the azimuth and elevation angles separately. This is a straightforward procedure using the EDBA method on each of the received signals on both ULAs at each axis. Then, after estimating the azimuth (*ϕ*_{
k
}) and elevation (*θ*_{
k
}) angles, the pairing is achieved by the alignment of the eigenvalues' magnitudes. From Section 3, it is shown that the EDBA method estimates the angles from the eigenvectors of the crosscorrelation matrix **R**_{21}. Since the eigenvalues' magnitudes of the crosscorrelation matrix **R**_{21} depend on the received signals' power (which are assumed to be the same on both ULAs on both axis), then the pairing between the estimated azimuth and elevation angles is achieved by aligning the estimated azimuth and elevation angles depending on their corresponding eigenvalues' magnitudes.

## 6 Estimating the received signals' power

This section shows how the received signals' power can be estimated after estimating the received signals' AOAs. This is achieved with an automatic pairing between the received signals' power with their corresponding AOAs. Pairing can be performed for the EDBA estimator or its 2D estimator extensions. For sake of simplicity, we will show how the received signals' power is estimated for the simple EDBA estimator explained in Section 3, and the extension for the 2D EDBA estimators can be easily deduced.

**a**(

*θ*

_{ k }) in (3) and (4) can be reformulated using the estimated angles $\left({\widehat{\theta}}_{k}\right)$ for

*k*= 1 →

*K*. This leads to the ability of reformulating the matrix

**A**(θ) in (5), and we will give it the notation $\widehat{\mathbf{A}}\left(\theta \right)$. Since the eigenvector matrix

**U**is available from (10), and the matrix $\widehat{\mathbf{A}}\left(\theta \right)$ is known, then the appropriate matrix (

**T**) in (12) can be estimated as follows

Similarly, the matrix **Z** depends on *θ*_{
k
} in its formulation as shown (6) and (7). Thus, from ${\widehat{\theta}}_{k}$, we can reformulate the matrix **Z**, and we will give it the notation $\widehat{\mathbf{Z}}$.

**Γ**

_{Z}is available from (10) and then from (13), the received signals' power matrix (

**P**

_{ s }) can be estimated as follows

where (.)^{+} is the pseudo-inverse operator.

Thus, the received signal power can be deduced from the diagonal elements of ${\widehat{\mathbf{P}}}_{s}$, and we will give it the notation ${\widehat{p}}_{k}$. The pairing between ${\widehat{\theta}}_{k}$ and ${\widehat{p}}_{k}$ is automatically provided from the fact that ${\widehat{\theta}}_{k}$ is estimated from the eigenvectors in **U** and ${\widehat{p}}_{k}$ is estimated from their corresponding eigenvalues in **Γ**_{Z}. Since each eigenvector in **U** corresponds automatically to a specific eigenvalue in **Γ**_{Z}, then ${\widehat{\theta}}_{k}$ is automatically paired with its corresponding ${\widehat{p}}_{k}$. Thus, the estimation of the received signal power is estimated with automatic pairing with its corresponding received signal AOA.

Similarly, the estimation of the received signal power can be easily applied to the 2D AOA estimation extensions for the EDBA explained in Section 5, resulting in estimating the azimuth/elevation angles jointly with the received signals' power with automatic pairing.

The performance of the proposed methods will be shown in the simulation section (Section 7).

## 7 Simulation results

Simulations of the proposed EDBA estimator with its extensions were completed to assess their performance. The elements of each antenna array were separated by a half-wavelength (i.e., $d=\frac{\lambda}{2}$). Unless mentioned otherwise, the number of antenna doublets was set to *M* = 10. The number of snap shots was set to *W* = 256 and *W* = 1,000 (where *W* is the number of snap shots over which the correlation matrices were estimated). The number of sources was set to 2. The near far ratio (NFR) was set to -10 dB, where the NFR is defined as $10\mathrm{log}\left({\scriptscriptstyle \frac{{A}_{2}^{2}}{{A}_{1}^{2}}}\right))$. The proposed EDBA and its extensions were compared with the ESPRIT method.

*θ*

_{1}= 75° and

*θ*

_{2}= 45°. The results in Figure 4 show that the proposed EDBA method gave better performance than the ESPRIT method.

*θ*

_{1}= 75° and

*θ*

_{2}= 45°. The azimuth angles for the two sources were set to

*ϕ*

_{1}= 80° and

*ϕ*

_{2}= 55°. The results in Figure 5 indicate that the proposed EDBA-2D method gave very close performance to the ESPRIT method with the less complexity advantage for the proposed EDBA-2D method. Also, the EDBA-2D performs the estimation of the azimuth and elevation angles with automatic pairing.

*ϕ*

_{1}to be taken from the following equation

*ϕ*

_{1}=

*ϕ*

_{2}+

*δ*where

*δ*is the angular deviation with

*θ*

_{1}= 75°,

*θ*

_{2}= 45°, and

*ϕ*

_{2}= 55°. The SNR for the first source was set to 10 dB. The results in Figure 6 indicate that the proposed EDBA-2D method gave better performance than the ESPRIT method for different AOA deviations.

*W*= 256 and

*W*= 1, 000, respectively. The number of antenna elements

*M*was set to 10. Both tables indicate that the proposed EDBA-2D and Two-EDBA algorithms managed to pair the azimuth and elevation angles successfully.

*W*= 256 and

*W*= 1, 000, respectively. The SNR was set to 15 dB for the first source. Both tables show that the proposed EDBA-2D and Two-EDBA algorithms managed to pair the azimuth and elevation angles successfully.

Thus, the proposed EDBA-2D and Two-EDBA methods have high capability of pairing the estimated azimuth and elevation angles with good accuracy and in an automatic procedure.

## 8 Conclusion

In this paper, we propose an AOA estimator that we named the EDBA method. The EDBA method is applied by taking the EVD of the received signal crosscorrelation matrix. The AOA of the received signals is contained in the eigenvectors of the crosscorrelation matrix. So, the AOA of the received signals is deduced from these eigenvectors. Two extension methods for 2D estimation are introduced. The first extension method estimates the elevation angles from the eigenvectors of the crosscorrelation matrix, and the corresponding azimuth angles are estimated from the corresponding eigenvalues. This method is named the EDBA-2D. The second extension method is named the Two-EDBA estimator and uses the alignment of the eigenvalues' magnitudes to pair the azimuth and elevation angles. Also, the EDBA method is extended to estimate the received signals' power with automatic pairing with their corresponding AOAs. Numerical simulation indicated that the EDBA method and its extensions outperformed the ESPRIT AOA estimator and other pairing methods. Also, the EDBA method and its extensions are low complex and do not require any searching or pairing procedure to perform the estimation.

## Declarations

## Authors’ Affiliations

## References

- Hew N, Zein N: Space-time estimation techniques for UTRA system. Capacity and range enhancement techniques for the third generation mobile communications and beyond (Ref. No. 2000/003).
*IEE Colloquium on*2000, 6/1-6/7.Google Scholar - Chen Y-F, Zoltowski M: Joint angle and delay estimation for DS-CDMA with application to reduced dimension space-time RAKE receivers. Acoustics, speech, and signal processing, 1999.
*ICASSP '99. Proceedings, 1999 IEEE International Conference on*1999, 5: 2933-2936.Google Scholar - Al-Jazzar S, Ghogho M, McLernon D: A joint TOA/AOA constrained minimization method for locating wireless devices in non-line-of-sight environment.
*IEEE Trans Veh Technol*2009, 59: 468-472.View ArticleGoogle Scholar - Deng P, Fan P: An AOA assisted TOA positioning system. Communication technology proceedings, 2000. WCC--ICCT 2000.
*International Conference on*2000, 2: 1501-1504.Google Scholar - Kikuchi S, Tsuji H, Sano A: Pair-matching method for estimating 2-D angle of arrival with a cross-correlation matrix.
*IEEE Antennas Wirel Propag Lett*2006, 5: 35-40.View ArticleGoogle Scholar - Roy R, Kailath T: ESPRITestimation of signal parameters via rotational invariance techniques.
*Opt Eng*1990, 29: 296-313. 10.1117/12.55606View ArticleGoogle Scholar - Haardt M, Nossek JA: Unitary ESPRIT: How to obtain increased estimation accuracy with a reduced computational burden.
*IEEE Trans Signal Process*1995, 43: 1232-1242. 10.1109/78.382406View ArticleGoogle Scholar - Xia T, Zheng Y, Wan Q, Wang X: Decoupled estimation of 2-D angles of arrival using two parallel uniform linear arrays.
*IEEE Trans Antennas Propag*2007, 55: 2627-2632.View ArticleGoogle Scholar - Tayem N, Kwon HM: L-shape 2-dimensional arrival angle estimation with propagator method.
*IEEE Trans Antennas Propag*2005, 53: 1622-1630.View ArticleGoogle Scholar - Wu Y, Liao G, So HC: A fast algorithm for 2-D direction-of-arrival estimation.
*Signal Process*2003, 83: 1827-1831. 10.1016/S0165-1684(03)00118-XView ArticleGoogle Scholar - Swindlehurst A, Kailath T: Azimuth/elevation direction finding using regular array geometries.
*IEEE Trans Aerosp Electron Syst*1993, 29: 1828-1832.Google Scholar - Zoltowski M, Haardt M, Mathews CP: Closed-form 2-D angle estimation with rectangular arrays in element space or beamspace via unitary ESPRIT.
*IEEE Trans Signal Process*1996, 44: 316-328. 10.1109/78.485927View ArticleGoogle Scholar - del Río JEF, Cátedra-Pérez MF: The matrix pencil method for two-dimensional direction of arrival estimation employing an L-shaped array.
*IEEE Trans Antennas Propag*1997, 45: 1693-1694. 10.1109/8.650082View ArticleGoogle Scholar - Liu TH, Mendel JM: Azimuth and elevation direction finding using arbitrary array geometries.
*IEEE Trans Signal Process*1998, 46: 2061-2065. 10.1109/78.700985View ArticleGoogle Scholar - Lu G, Ping W, Jianfeng G: Automatic pair-matching method for estimating 2-D angle of arrival.
*Int Conf Commun Circuits Syst*2008, 914-917.Google Scholar - Luo L, Gu J-F: Two-dimensional DOA estimation by cross-correlation submatrix.
*11th IEEE Singapore International Conference on Communication Systems 2008. ICCS 2008*2008, 514-518.Google Scholar - Han Y, Wang J, Zhao Q, Song X: L-shape 2-D DOA estimation with second-order statistics for coherently distributed source.
*4th International Conference on Wireless Communications, Networking and Mobile Computing, 2008. WiCOM '08*2008, 1-4.Google Scholar - Bai L, Peng C-Y, Biswas S: Association of DOA estimation from two ULAs.
*IEEE Trans Instrum Measurement*2008, 57: 1094-1101.View ArticleGoogle Scholar - Jian C, Wang S, Lin L: 2-D DOA estimation by minimum-redundancy linear array.
*The 8th International Conference on Signal Processing*2006.Google Scholar - Gan L, Gu J-F, Wei P: Estimation of 2-D DOA for noncircular sources using simultaneous SVD technique.
*IEEE Antennas Wirel Propag Lett*2008, 7: 385-388.View ArticleGoogle Scholar - Gu J-F, Wei P: Joint SVD of two cross-correlation matrices to achieve automatic pairing in 2D angle estimation problems.
*IEEE Antennas Wirel Propag Lett*2007, 6: 553-556.View ArticleGoogle Scholar - Al-Jazzar SO, Mclernon D, Smadi MA: SVD-based joint azimuth/elevation estimation with automatic pairing.
*Signal Processing*2010, 90: 1669-1675. 10.1016/j.sigpro.2009.11.017View ArticleGoogle Scholar - Roy R, Kailath T: Esprit-estimation of signal parameter via rotational invariance technique.
*IEEE Trans Acoust Speech Signal Process*1989, 37: 984-995. 10.1109/29.32276View ArticleGoogle Scholar

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