- Open Access
Advanced spectrum sensing with parallel processing based on software-defined radio
EURASIP Journal on Wireless Communications and Networking volume 2013, Article number: 228 (2013)
Due to interference between co-located wireless networks, obtaining accurate channel assessment becomes increasingly important for wireless network configuration. This information is used, among others, for cognitive radio solutions and for intelligent channel selection in wireless networks. Solutions such as spectrum analyzers are capable of scanning a wide spectrum range, but are not dedicated for channel occupation assessment because they are extremely costly and not able to perform continuous recording for a time period longer than a few seconds. On the other hand, low-cost solutions lack the flexibility and required performance in terms of configuration and sensing efficiency. To remedy the situation, this paper presents an alternative for channel assessment on top of a commercial software-defined radio platform. Although there exist software solutions for performing spectrum sensing on such platforms, to the best of our knowledge, continuous spectrum sensing and long-term recording remain challenging. We propose a pioneering solution that is capable of seamless spectrum sensing over a wide spectrum band and guarantees sufficient flexibility in terms of configurations. The proposed solution is validated experimentally. We demonstrate two advantages of seamless spectrum sensing: the capability of accurate channel occupancy measurement and detecting transient signals such as Bluetooth.
As the density of co-located wireless networks grows, wireless systems are more and more susceptible to mutual interference, leading to degraded network performance. At the same time, end users demand high quality of service from wireless networks. This conflict gains increased interest in both the industrial and the academic world, resulting in several research projects[1, 2]. Cognitive radio (CR) is a promising technology for solving the above problem. Originally, CR is a frequency-agile radio, capable of accessing licensed spectrum without influencing the primary users. The concept of CR can be extended for more efficient sharing of unlicensed band among heterogeneous technologies.
The fundamental requirement for CR is the ability to correctly examine the spectrum usage. One approach is to register the primary user’s location and power coverage into a central database, which obviously does not apply for a dynamic environment. Another approach is to perform channel assessment locally, allowing fast reaction to changes in the spectrum.
The localized spectrum sensing approach appears to be more appealing, thanks to its adaptivity to a changing spectrum environment. Most wireless devices have only one radio module. Therefore, it is common to interleave the channel assessment and data transmission activity. How to find the optimal sensing frequency is crucial to improve the system performance and hence becomes a popular research topic on itself[4, 5]. However, it is not always convenient to limit transmission into predefined intervals. Sensing a broad spectrum range with limited radio front-end capability and processing resources results in limited sensing performance.
An alternative is to add a few more advanced devices dedicated for sensing above the original network. Such devices are referred to as sensing engines. Apart from the CR context, sensing engines can help operators of wireless technology to better identify the location and characteristics of the interference. In addition, for wireless researchers, an accurate sensing engine can provide a more detailed view on the physical layer. One use case could be a MAC layer researcher that needs to identify the interpacket interval or the duty cycle of a channel.
One of the most crucial aspects of the sensing engine is its efficiency because discontinuity in spectrum sensing often leads to inaccurate assessment and missed detection of interference or primary usage. Spectrum sensing generally consists of two phases:
The sampling phase, in which raw samples are collected from the air
The processing phase, in which buffered samples are processed for spectrum analysis
Depending on the processing speed, the processing phase can partially or completely happen in parallel with the sampling phase. The time used for collecting samples from the air is referred to as the sampling time, while the time required by the processing phase in addition to the sampling time is referred to as the processing time. The sensing efficiency is then defined as the ratio of the sampling time and the summation of the sampling time and the processing time. During the processing time, the sampling of the wireless medium is put onto hold, which means that the sensing engine is ‘blind’. It is possible that a number of transient signals are missed during this period. The time interval when sampling activity is put onto hold is referred to as the blind time. Ideally, the blind time should be reduced to zero, meaning 100% sensing efficiency to achieve seamless detection.
There are various sensing devices on today’s market. Solutions such as spectrum analyzers are capable of scanning a wide spectrum range, but are not dedicated for channel assessment and extremely costly. For instance, a spectrum analyzer usually cannot do continuous recording for a time period longer than a few seconds, and the recorded spectrum needs to have high frequency resolution for visualization purposes. However, the raw spectrum information still requires further processing to obtain the energy for specified channels. On the other hand, low-cost solutions are trimmed for simple and steady recording but lack the flexibility and required performance. For instance, they are not able to achieve seamless spectrum sensing and usually have nonconfigurable frequency span and resolution bandwidth.
The key requirements for channel assessment in the CR context are flexibility, reliability, and the capability of continuous recording. Energy per channel with a timestamp is the desired output format; an excessively fine frequency resolution is generally not appreciated. To enable cooperative or distributed spectrum sensing, the measurement should be obtained with a relatively low-cost platform. Finally, from a developer’s point of view, the implementation should be flexible and transparent in order to achieve fast prototyping and testing. After realizing the gap between the capability of high-end spectrum analyzers and the need of cognitive radio researching, we decide to build an alternative - a simpler but more dedicated sensing engine.
In summary, to achieve an advanced wireless system, we need sensing engines with relatively low cost and that are capable of continuous sensing and recording. To this end, this paper presents a solution that is built upon a commercial software-defined radio (SDR). The solution is further extended on multiple SDR devices for cooperative and distributed spectrum sensing. While the developed solution has less functionality than spectrum analyzers, it is also much cheaper and dedicated for channel assessment. Above all, in contrast to most spectrum analyzers, our solution is capable of continuous sampling and recording.
The remaining part of the paper is organized as follows: first, we present an overview of the most common sensing devices today; next, we describe how we arrive at our solution and its advantages; and finally, the detailed software structure and configurations of the sensing software are presented. The proposed solution is verified experimentally, with real-life wireless signals, such as Wi-Fi and Bluetooth.
2 Analysis of existing platforms
This section presents some of the most representative sensing solutions, starting from powerful but expensive spectrum analyzers to simple off-the-shelf sensor devices. The processing mechanism of high-end spectrum analyzers is discussed in depth, as it is needed for the further sections.
2.1 Spectrum analyzers
In today’s market, most spectrum analyzers have two basic modes: swept mode and fast Fourier transform (FFT) mode. The swept mode is the traditional spectrum sensing method, where the radio-frequency (RF) center frequency is incremented by a small step very rapidly, hence the name ‘swept analyzer’. The signal obtained at each step is passed through a resolution bandwidth RBW filter, and the amplitude is then calculated by a detector. The range of the sweep defines the frequency span. The time needed for the front-end to scan the entire frequency span is called the sweep time. The major disadvantage of a swept analyzer is that the spectrum can only be measured at one frequency point at a time. Therefore, it is possible to miss short signal events during the sweeping, as illustrated in Figure1.
FFT-based spectrum analyzers do not need the sweeping of RF front-end. The transformation from time domain to frequency domain is achieved by FFT instead. First, a batch of samples are stored in memory, and then by applying FFT, the time domain samples are translated into spectrum information. The frequency span of the FFT-based analyzer depends on the sample rate. Although no sweeping is actually performed, we inherit the term ‘sweep time’ to describe the time between two consecutive FFT results.
Some spectrum analyzers combine the swept mode and the FFT mode. The result of one sweep is then a combination of several FFT shots obtained at different center frequencies. This is termed as the swept FFT mode.
The advantage of the FFT-based analyzer is that it is possible to look at a broader range of the spectrum with one operation. However, FFT requires first the acquisition of a batch of samples and then followed by a processing step. What happens in between subsequent acquisition phases is missed by the analyzer, as illustrated in the upper part of Figure2.
To solve this problem, the analyzer needs to meet the following conditions:
The processing speed should be faster than the acquisition speed.
The sample acquisition and sample processing should happen in parallel.
The above requirements are also described in the lower part of Figure2. Spectrum analyzers that are capable of seamless measurements are referred to as real-time spectrum analyzers. The exact features of real-time analyzers depend on the type of the device. To illustrate this, two specific spectrum analyzers are described in more detail in the following section: the FSVR series of ROHDE & SCHWARZ and the RSA series of Tektronix. Although modern spectrum analyzers also include the swept mode to increase the frequency range, here we only focus on the FFT mode. The discussion below does not include implementation details but instead emphasizes the underlying processing mechanism and the amount of flexibility for the end users.
2.1.1 ROHDE & SCHWARZ FSVR
The FSVR is a popular series from R&S. The machine performs 250,000 times 1,024-point FFT per second, resulting in one FFT shot every 4 μs. When users configure the frequency span (sample rate), the amount of overlapping between adjacent FFT frames is automatically adjusted, as illustrated in Equation 1, where Fs is the sample rate and X is the amount of overlapping of samples between adjacent FFT frames in percentage:
The obtained FFT shot cannot be displayed directly because the number of FFT bins is generally greater than the available pixels on the screen. Various detectors are used to combine multiple FFT bins into one bin for visualization. Apart from the pixel limitation, most screens can only refresh 60 times per second; hence, FSVR combines multiple FFT shots into one for display purposes, and this is referred to as the trace detector. In the spectrogram mode, the number of combined FFT shots is defined by the parameter sweep time. To a certain extent, users can lower the sweep time to increase the time resolution. The resolution bandwidth however is dependent on the frequency span, due to the fixed FFT size.
2.1.2 Tektronix RSA6000
Unlike FSVR, the RSA spectrum analyzer from Tektronix exposes more parameters to the end user. For instance, there is a parameter to specify the length of the time interval during which samples are collected and analyzed seamlessly. Both FFT size and sample rate can be configured independently. This decouples the resolution bandwidth from the frequency span. Similar to FSVR, the final result is trimmed by various detectors for displaying on the screen.
RSA provides highly flexible processing features, based on post-processing of raw samples in the memory.
For instance, in the spectrogram mode, users can zoom in or zoom out on the time scale by adapting the amount of overlapping between FFT frames. However, when doing so, the machine needs to recalculate the spectrogram, and this may take a considerable amount of time depending on the quantity of samples. Between each block of continuous samples, a black line is used to indicate the discontinuity of the spectrogram.
Regardless the difference in processing style, the two analyzers do have one thing in common - the output is produced in a way that is best suited for displaying on the screen. Also, in contrast with the fancy display features, the recording features of spectrum analyzers are relatively basic. Both FSVR and RSA are capable of recording raw samples and some amount of spectrogram, depending on the waveform memory depth. Take the FSVR as an example, the waveform memory allows the user to store maximum 200 million in-phase and quadrature-phase (IQ) samples. This means a recording of 8 s with 25 mega samples per second (Msps) of sample rate, which is just wide enough to cover one Wi-Fi channel. Apart from the time limitation, further processing on the raw IQ samples is still required to obtain the energy in specific channels.
In summary, spectrum analyzers are made for fast visualization of various signals and performing sophisticated off-line analysis. The capability of spectrum analyzers are far beyond FFT or storing raw samples; however, they lack the capabilities of continuous recording and fast data transfer, hence are not suitable for basic channel assessment.
2.2 Low-cost USB devices
There are several commercial sensing solutions running on a regular computer with a USB dongle. The USB dongle functions as the RF front-end while the host computer provides the user interface and the visualization functionality. Some of the well-known devices are Wi-Spy and Airmagnet.
The radio of Airmagnet has a 20-MHz intermediate frequency (IF) bandwidth. The Airmagnet spectrum analyzer makes use of the swept FFT mechanism to cover a bandwidth that is wider than 20 MHz. For the 2.4-GHz industrial, scientific, and medical (ISM) band, the entire frequency span is fixed to 83 MHz with 156-kHz resolution bandwidth. During each sweep, the radio increases its center frequency with a step of 20 MHz and dwells on each center frequency for 30 ms. The sweep time is fixed to 1 s. The fact that the frequency span is less than five times the IF bandwidth infers that each measurement of the 2.4-GHz ISM band contains maximum five blocks of samples. This means that the time to sample the wireless medium for each sweep is at maximum 150 ms. Given the constant sweep time of 1 s, the actual sensing efficiency is only 15%.
The mechanism of Wi-Spy resembles the pure swept spectrum analyzer. It uses a narrow-band RF receiver to scan across the interested band in tiny steps. The step width depends on the Wi-Spy model and the selected band of interest, ranging from about 50 to over 600 kHz. Compared to spectrum analyzers, the front-end of USB devices is less advanced, resulting in lower sensitivity and narrower spectrum coverage. Besides the less advanced RF front-end, USB-based sensing solutions rely on host machine softwares for processing, which are typically bound to certain operating systems. This further limits their usage. The feature of long-term recording is provided but with very limited efficiency and flexibilities.
2.3 Sensor devices
Another option is to use cheap sensor devices for spectrum analysis. Here the sensor devices refer to the battery-operated, low-power wireless platforms[11, 12]. Sensor chips are originally meant to form sensor networks for home automation or various monitoring purposes. They usually consist of integrated sensors, a microcontroller, and an IEEE 802.15.4 (Zigbee)-compliant radio module. The radio module provides built-in clear channel assessment (CCA), which can be used to evaluate the energy of the selected channel. With appropriate firmware, cheap sensor devices can also be programed into a swept spectrum analyzer.
It is evident that the CCA module can only sense one channel at a time and the frequency resolution is as wide as the Zigbee channel width. Although there exist solutions for programming front-end to perform fast sweeping in the 2.4-GHz ISM band, its low resolution bandwidth limits the detection accuracy.
2.4 Sensing solution overview
Table1 gives an overview of the advantages and disadvantages of different sensing solutions. High-cost solutions such as spectrum analyzers are usually overkill for the targeted applications: many functionalities built in spectrum analyzers are redundant for merely channel assessment. In addition, these devices are not capable of long-term and seamless recording and fast data transfer. On the other hand, low-cost devices have less bandwidth and limited processing power and flexibility. To remedy this situation, we aim to design a low-cost solution that is capable of seamless recording and offers sufficient flexibility, as listed as the last entry of Table1.
3 Our sensing solution
3.1 Design constraints
As discussed in Section 2.1, among the common spectrum analyzing approaches, the FFT mode is more advanced than the swept mode. Therefore, our SDR-based sensing solution makes use of an FFT-based sensing solution. Our solution has the following design goals:
Direct access to the IQ samples. This is a strict requirement since FFT relies on raw IQ samples instead of decoded bits or packets.
Sufficient sample rate. The frequency span is defined by the sample rate; hence, the higher the sample rate, the broader the detection range.
Flexibility. To be useful in a wide range of technologies, the solution should expose sufficient flexibility to the end user. It should be possible to configure the sensing engine to assess different sets of channels and to change the front-end gain settings or FFT size.
Ease of development. The design should be kept simple and transparent for fast prototyping and development.
Platform independence. To overcome any limitations caused by operating systems, the software should be platform independent.
These requirements are the main motivation to use a SDR platform.
3.2 The hardware platform
SDR platforms allow traditional radio functions, such as decoding or encoding, to be shifted from hardware to software. SDRs can be divided into two categories based on the type of processor used for signal processing: the first category makes use of a general-purpose processor in a regular computer; the second category relies on embedded processors onboard.
The Universal Software Radio Peripheral (USRP) formally developed by Ettus Research falls into the first category. It is a commercial SDR platform that utilizes a general-purpose processor and has gained widespread usage. The USRP consists of two parts: a fixed motherboard and a plug-in daughterboard. The motherboard contains an analog-to-digital converter (ADC) and a digital-to-analog converter (DAC), a field-programmable gate array (FPGA) for digital down conversion with programmable decimation rate, and an interface connected to the host PC. The daughterboard provides basic RF front-end functionality. The USRP N210 - the network series of the second USRP generation - outperforms the original series with its more powerful FPGA, faster ADC/DAC, gigabit Ethernet host connection, and complete remote configuration features. In addition, USRP has a broad range of daughterboards that cover frequencies from nearly DC to almost 6 GHz. A simplified diagram of the USRP N210 is illustrated in Figure3. Besides the hardware, Ettus Research also provides the universal hardware driver (UHD) for communicating between USRP and host PC. It is entirely open source and available for all major operating systems and can be built with many popular compilers such as the GNU Compiler Collection. Users are able to use the UHD driver stand-alone or with third-party platforms such as GNU Radio.
The Wireless Open-Access Research Platform (WARP) is an example SDR platform that falls into the second category. It has a powerPC processor and a large amount of programmable hardware resources. Compared to USRP, WARP provides higher onboard processing capacity but is also much more expensive. The WARP programming environment relies on the Xilinx FPGA software, which is not free for use. The embedded processing power and rich FPGA resource make it possible to build a stand-alone sensing system; however, due to the hardware programming and embedded environment, it is also more difficult to design and debug. In addition, there are less RF boards available in the WARP repository than in the USRP.
Because of the aforementioned reasons, the USRP was selected to design our SDR sensing platform. The lack of processing power on the USRP can be compensated by connecting it to a powerful host machine. Though there is an option to use GNU Radio like third-party platforms, our software is implemented directly above the UHD driver. This reduces the overhead of function calls, hence gives better performance and sensing efficiency. Apart from the UHD library, the Boost and FFTW libraries are also required. All of the required libraries work on major operating systems, including UNIX and Windows variants, thus making our solution platform independent.
The sensing engine software is currently compiled and tested on six identical hexa-core Linux servers. The choice of using a hexa-core server does not strictly comply to the initial low cost requirement; however, it is necessary to achieve sufficient amount of parallel processing, as further explained in Section 3.3. The architecture of the software can easily be ported to an FPGA platform. Note that the price of one USRP and one server is still significantly lower than the price of one spectrum analyzer; therefore, even the current approach is already an improvement in terms of overall financial cost.
The servers are physically located within a large-scale wireless testbed: the w-iLab.t testbed. Currently, six USRPs are deployed in the testbed, each connected to one of the hexa-core servers. The w-iLab.t uses OMF (cOntrol Management Framework) as its testbed control and management framework. OMF allows experimenters to configure multiple devices simultaneously, providing easy data logging services. Therefore, the multiple USRPs can easily be set up as a distributed cooperative sensing system. This configuration will be used for the Bluetooth detection experiment in Section 4.3.
3.3 The software architecture
As stated in Section 2, it is important that the processing time is shorter than the sample acquisition time in order to achieve continuous spectrum sensing.
When no parallelism is present, the sample acquisition alternates with the processing phase, and as such, the blind time of the sensing engine is equal to the processing time (as illustrated in plot (a) of Figure4).
When pipelining between sample acquisition and processing is introduced, after the first batch of samples arrived, sampling and processing the samples obtained in the previous time frame are happening in parallel. This is the first level of parallelism. The blind time is equal to the original processing time minus the sampling time, as shown in plot (b) of Figure4. However, this is not sufficient to achieve seamless sampling if the processing time is longer than the sampling time. To further reduce the processing time, we seek to add parallel processing within the processing phase itself. The processing phase consists of splitting samples into small frames, applying FFT operation on all frames sequentially, and combining all the FFT result in one way or another. As FFT is a highly computational demanding operation, instead of having one single FFT core working sequentially, we utilize multiple FFT cores to work simultaneously: the incoming samples are divided among the multiple FFT cores for processing. Once the samples have been received, the FFT cores work independently from each other, hence ideal for parallelism. This is where the second-level parallelism is introduced. We illustrate the case of two FFT cores working in parallel in plot (c) of Figure4. More FFT cores could be added if it is necessary to achieve continuous spectrum sensing.
The sensing engine software relies on multi-threading to achieve parallel processing. There are two main threads running at any moment: one thread is responsible for collecting samples from the USRP (referred to as the sample-collecting thread), and the other thread is responsible for processing the samples (referred to as the sample-processing thread). The sample-processing process again generates several sub-threads to process the incoming samples in parallel. The sample processing in our solution calculates the FFT-based power spectrum density (PSD) and the energy for specified channels. Once all sub-threads finish processing, they terminate and the original sample-processing thread outputs the result to either a local file or the standard output. To simplify the collection of measurements in the w-iLab.t testbed, the measurements are first printed to the standard output and then piped to a predefined database using an OMF wrapper. The general structure is illustrated in Figure5.
To achieve true parallel pipelining, two buffers are used to collect samples from the USRP. At any given moment, when one sample-collecting thread is writing to one buffer, the sample-processing thread will be reading from the other buffer. Therefore, once the first batch of samples has arrived, the two main threads work fully in parallel. To ensure that the two main threads do not read and write to the same buffer at the same time, the sample-processing thread needs to work faster than the sample-collecting thread. Hence, within the sample-processing thread, several sub-threads are created to accelerate the processing. The number of threads that should be used to achieve the best efficiency depends on how many samples the buffer contains and the FFT size. During our experiments, eight processing threads are sufficient to support a sample-collecting thread at the highest sample rate of the USRP (25 Msps). However, for configurations in which only a small amount of samples is collected, the overhead of creating multiple threads outweighs its processing benefit; hence, the sample-processing thread can no longer follow the sample-collecting thread. When this happens, the software detects the overflow of samples and return an error message.
3.4 Configurations and important features
The sensing engine software can be configured using various options, which are described in detail in this section.
3.4.1 Continuous FFT mode vs. swept FFT mode
First of all, the sensing engine can be used in two modes: the continuous FFT mode and the swept FFT mode.
For the continuous FFT mode, the USRP front-end stays at the same frequency and continuously samples the wireless medium. Similar to spectrum analyzers, users can control both the center frequency and the sample rate in order to define the spectrum range.
For the swept FFT mode, the USRP will always collect samples at its maximum sample rate of 25 Msps. The samples collected at a specific RF center frequency are called a block, while the complete measurement across several RF center frequencies is called one sweep. Between two adjacent blocks, the center frequency is incremented by a step of 20 MHz. Users can specify the center frequency of the beginning block and how many blocks one sweep should contain. As such, by adding the swept FFT mode, the frequency span is no longer limited by the sample rate.
3.4.2 Measurement types
The sensing engine can be configured to perform different types of measurement:
The sensing engine can measure the PSD in the required frequency range and thus calculates the amount of energy detected in each specified channel. This is referred to as the PSD measurement. The PSD measurement has three variants: averaging, maxhold, and minhold, comparable to the function of the detector for spectrum analyzers. Typically, the number of samples per buffer is a lot larger than the FFT size; hence, each buffer contains many FFT frames. For the PSD measurements, the software does either averaging, maxhold, or minhold across different FFT frames, and the final FFT result is used for the power integration for the requested channels. The maxhold mode is useful to detect the signal’s presence, while the minhold mode can be used for estimating the noise floor.
For the continuous FFT mode, the sensing engine can also measure how much portion of time the energy of the specified channels is above a certain threshold. This is referred to as the duty cycle measurement. To realize this function, the software investigates a particular channel and counts how many times its energy is above a threshold, and then divides this number by the total number of FFT frames in the buffer. When the appropriate threshold is selected (a value that is slightly above the noise floor), the duty cycle mode can be a powerful tool to detect transient signals.
3.4.3 Sensing efficiency
Recall that the sensing efficiency is defined as the ratio of the sampling time and the summation of the sampling time and the additional processing time. In our case, the processing phase happens entirely in parallel with the sampling phase. Hence, no additional time is required by the processing phase. For the continuous FFT mode, the sensing efficiency is always 100% since the USRP never stops sampling.
For the swept FFT mode, the sampling phase must be interrupted for channel switching, which is the only cause for time loss. Hence, the the sensing efficiency for the swept FFT mode is defined as
Unfortunately, channel switching of the USRP is more complicated than only tuning the radio front-end’s center frequency. The host machine needs to communicate with the embedded processor on the USRP over the Ethernet interface. The exact handling of channel switching depends on the firmware on the embedded processor and the driver of the host machine.
To measure the channel switching time, Wireshark was used to record the packets between the USRP and the host machine. All configuration packets have a short packet length, while the packets containing IQ samples are typically 1,514 bytes long. By using a packet-length-based filter, only the configuration packets used for channel switching and streaming commands can be displayed. Based on this output, Wireshark can generate an IO graph, plotting the packet per millisecond vs. the time, as shown in Figure6. This graph gives an indication on how much time is spent on sampling and how much time is spent on channel configuration. The sampling time is directly related to the requested number of samples by one stream command. This is defined by the option ‘– spb’ in the sensing software, standing for sample per buffer. The packet trace shown in Figure6 is generated with 524,288 samples per buffer; the sampling time for each block is 524,288/25 Msps = 21 ms, this result corresponds with Figure6. The configuration time for channel switching cannot be influenced by software options. It currently requires about 19 ms to switch a channel for the USRP. The channel switching time is a hardware and driver issue, and it can be reduced by improving the driver and firmware. Although this is not the focus of this paper, it is an interesting direction for future improvements.
Up till now, we have identified the channel switching time, and the sensing efficiency in the swept FFT mode can be calculated by Equation 2. Increasing the sampling time is an effective way to improve the sensing efficiency. When configuring the sensing engine with ‘spb’ equal to 4,194,304, the sampling time is 4,194,304/25,000 kHz = 168 ms and the sensing efficiency is 168 ms/(168+19) ms = 89.8%. With five blocks per sweep, the sensing engine can cover 100-MHz bandwidth and produce one sweep per second. Note that this configuration is very similar to the measurement capabilities of Airmagnet; however, the sensing efficiency of Airmagnet is only 15%.
3.4.4 Time resolution
In the swept FFT mode, the sensing engine produces one line of output per sweep. The continuous FFT mode can be considered as a special case of the swept FFT mode, where the sweep consists of only one block of samples. We use the term sweep time to describe the time interval between two subsequent lines of measurements.
When measuring the PSD, the time resolution depends on the sweep time. For the continuous FFT mode, the sweep time is equivalent to the sampling time. For a given sample rate, the sweep time is proportional to the sample per buffer - the spb parameter. Reducing the spb parameter will reduce the sweep time, making the output more suitable for resolving short signal events.
For the swept FFT mode, the sweep time is equal to
Although for the swept FFT mode the sweep time depends on the channel switching time and proportional to the number of blocks in a sweep, it still heavily relies on the sampling time. Hence, to a certain extent, we are able to improve the time resolution by reducing the buffer size.
For the duty cycle measurement in the continuous FFT mode, the time to resolve an event depends on the FFT size. This is because the entire buffer of samples is divided into multiple FFT frames. The length of the FFT frame serves as the basic unit for the channel occupation calculation.
Since commercial USB sensing solutions typically have no or limited sweep time configurations, our solution is clearly more flexible in this aspect.
3.4.5 Channel configuration
It is important to let the sensing engine know which channels to measure. Four configuration options are used to complete this target:
numofchannel: specifies the number of channels to be measured
firstchannel: the center frequency of the first channel
channelwidth: the bandwidth of each channel
channeloffset: the difference between adjacent channels’ center frequency
At this moment, software only allows to specify channels that are uniformly spaced and with identical bandwidth. This format is flexible enough to describe the channel specifications of the most popular wireless standard. As an example, to measure the 13 channels of Wi-Fi in the 2.4-GHz range, the following options are used in the input command: ‘–numofchannels 13 –firstchannel 2412000000 –channelwidth 22000000 –channeloffset 5000000’. The above options tell the sensing engine to measure 13 channels, with the first channel starting at 2,412 MHz, each channel 22 MHz wide, and the center of all the channels 5 MHz apart. This feature makes it easy to conduct measurements for different technologies.
3.4.6 Output format
The output of the sensing engine contains the following components:
timestamp: a unix timestamp in microsecond precision
usrpid: the id of the USRP used to collect samples
energy or duty cycle array: an array that contains either the energy (in dBm) or duty cycle (in percentage) for all channels of interest
In contrast to the raw spectrum measurements from spectrum analyzers and some USB-based devices, the output format can directly be used for channel assessment.
3.4.7 Resolution bandwidth and FFT size
Usually, the RBW of the FFT-based spectrum analyzer is calculated as the ratio of sample rate over FFT size. Similar to the Tektronix RSA analyzer, users can also directly specify the FFT size and sample rate independently. The final frequency resolution that is obtained is defined by the number of channels and the channel’s bandwidth. So the RBW does not directly rely on the FFT size. However, it is still necessary for the underlying RBW of FFT to be sufficiently smaller than the interested channel bandwidth; otherwise, the power integration for the specified channel will be less accurate.
3.4.8 Performance comparison with existing sensing solutions
Having introduced the various configurations for our solution, this section compares the performance of our spectrum analyzing solution with commercially available devices. A summary is available in Table2. A few things need to be kept in mind to understand this table:
Firstly, we are comparing a broad range of devices. For a fair comparison, we need to fix one set of parameters and observe the remaining parameters. However, due to the fact that some devices are less flexible than others, it is not feasible to configure all devices so that they achieve exactly the same settings. To resolve this issue, a simple rule is applied: the most flexible devices are configured to have the same settings as the most inflexible device. For our comparison, Airmagnet is the most inflexible device among the presented solutions. Therefore, all other devices are configured to the same settings as Airmagnet.
Secondly, the performance parameters are not completely independent. We already stated the trade-off between frequency resolution and time resolution, which applies to all devices. Another example is device specific: for the FSVR spectrum analyzer, the ratio of the span over RBW is predefined, depending on which FFT window is selected. In Table2 this ratio is 400, when the rectangular window is applied. Therefore, we need to decide which parameters are controlled and which parameters are observed. For this comparison, sensing efficiency was chosen as the primary observed parameter. The entire frequency span is chosen to be the major controllable parameter, listed as ‘span’ in Table2. Real-time span refers to what bandwidth the sensing engine can cover without performing sweeping; the maximum real-time span usually depends on the hardware capability of the platform. It is listed here for completion.
When a parameter is configurable, it is marked with a superscripted lowercase letter ‘a’. The settings presented in Table2 are just one set of configurations; readers are encouraged to check the reference materials for more details.
The continuous FFT mode and the swept FFT mode of the USRP sensing engine are listed as two separate entries: ‘USRPSE(cont)’ and ‘USRPSE(swept)’. This way, it is possible to fully evaluate the capability of our solution.
When certain settings are unavailable for a specific device, the setting closest to the Airmagnet configuration is listed in the table. For instance, the span of the FSVR analyzer is listed as 40 MHz in Table2 because this is its maximum real-time span in FFT mode. The same reason applies for putting 25 MHz as the span of the USRP sensing engine in continuous FFT mode.
When certain parameters are independent of the sensing efficiency, the optimal performance of that device is listed. For instance, the sweep time of FSVR is listed as 100 μs which is the shortest sweep time the device can achieve, and the same applies to the sweep time of the USRP in continuous FFT mode.
The sensing efficiency of the USRP sensing engine has been discussed in Section 3.4.3. The efficiency of Airmagnet is derived in Section 2.2. For Wi-Spy, the concept of sensing efficiency is not applicable because it operates purely in sweeping mode. The rest of the values are obtained from the corresponding reference material[9, 10, 26].
Table2 demonstrates the performance advantages of our solution. The continuous FFT mode of the USRP sensing engine is the only solution which is capable of 100% sensing efficiency and long-term recording at the same time. The swept FFT mode offers 89% sensing efficiency under a configuration similar to that of Airmagnet, which only provides 15% sensing efficiency. Although the sweep time of our solution is longer than the best record of the (more expensive) FSVR spectrum analyzer, it is still much faster than Airmagnet and Wi-Spy devices.
4 Experiments and results
This section focuses on experimental analysis for the proposed solution. We first describe the experiment platform in Section 4.1, and then we present two experiments in depth in Sections 4.2 and 4.3. In both experiments, we use our sensing engine solution for detecting certain types of signal and evaluating the performance. The difference is that the first experiment uses Wi-Fi beacon frames as target signal, while the second experiment uses regular Bluetooth traffic. The reason that we choose the Wi-Fi beacon is that it appears periodically at a fixed frequency band, so it is a well-defined signal. Bluetooth, on the other hand, uses random frequency hopping, therefore is one of the most challenging signals to detect in the ISM bands.
Within each experiment, we first introduce the characteristics of the target signal and then describe what settings are used on our sensing engine to detect the target signal, followed by measurements and thorough analysis.
4.1 The w-iLab.t testbed
The experiments are conducted on the w-iLab.t testbed. The topology of the testbed is shown in Figure7, where the locations of the USRPs are highlighted with yellow stars. Apart from USRPs, the majority of the devices in the w-iLab.t testbed are embedded PCs equipped with Wi-Fi interfaces, IEEE 802.15.4 sensor nodes, and Bluetooth dongles. All devices are reachable over a wired network interface for management purposes. Each device can be fully configured by the experimenters. When the wireless devices are configured via the same embedded PC, they are said to be attached to one ‘node’. The regular nodes are indicated with blue dots in Figure7. The rich combination of heterogeneous technologies is ideal for testing the proposed sensing solution. As mentioned before, two representative wireless signals are used to test the performance of our sensing engine - the beacon of a Wi-Fi access point (AP) and regular traffic between a pair of Bluetooth devices. The locations of the Wi-Fi AP and the Bluetooth devices used for experiments are indicated in Figure7.
4.2 Wi-Fi beacon experiment
The Wi-Fi beacon appears periodically on a fixed channel. According to the IEEE 802.11 standard, a beacon frame is 134 bytes long and transmitted at 1 Mbit/s. Hence, one beacon transmission takes around 134 × 8/1 Mbit = 1.072 ms. The beacons are transmitted on channel 1 and the beacon interval is set to 100 ms. As such, the channel will be occupied for about 1% of the time. This well-defined signal is convenient to validate the channel occupation measurement.
4.2.1 Measurements using continuous FFT mode
In order to resolve beacon frames, the buffer size was set to 32,768. Given the sample rate of 25 MHz, the sampling time is around 1.3 ms, comparable to the beacon transmission time. The sensing engine was then configured to sense the Wi-Fi channel with 1-MHz resolution bandwidth in the continuous FFT mode.
A spectrogram is the best way to show the seamless capturing of the Wi-Fi beacons. The recorded spectrogram is shown in Figure8. During 400 ms, four beacons are transmitted and they are all captured with their full signal strength. This clearly demonstrates the advantage of seamless capturing. Note that the presented spectrogram is only 400 ms long; in reality, the period of this recording can be indefinite.
The above measurement with extremely fine time resolution is only needed for visualization purposes, but is not required for channel assessment. In order to reduce the output per second while still being able to reflect the actual usage of a channel, the channel duty cycle was measured with −70 dBm as the detection threshold. Note that −70 dBm is slightly above the noise level measured by the USRP for Wi-Fi channels, which gives the best probability of detection based on our experience. There are many theories related to the energy detection threshold in order to improve the probability of detection. In the context of our experiment, all the nodes are in line-of-sight topology; hence, the detection threshold is not critical. The complexity of determining the optimal energy detection threshold is out of the scope of this paper.
When the spb parameter is set to 16,777,216, the sampling time is around 0.67 s. The sensing engine measures that the selected Wi-Fi channel is occupied between 0.95% and 1.05%. This corresponds to the calculated duty cycle. The reason of the 0.1% fluctuation is because the sampling time is not a multiple of the beacon interval; hence, the exact number of detected beacons per buffer varies. This measurement demonstrates that our sensing engine is capable of seamless capturing and performing accurate channel occupation assessments.
4.2.2 Measurements in swept FFT mode
For the measurement in the swept FFT mode, all 13 Wi-Fi channels in 2.4 GHz are measured. The spb parameter is increased by a power of 2, from 131,072 to 4,194,304. The spectrograms of 12 s are shown in Figure9. Note that at the time of this experiment, apart from our test beacon on channel 1, there is another external access point active on channel 10. This paper focuses only on the analysis of the beacon signal on channel 1.
First, as expected, when the spb value is small, the sensing engine uses a shorter sweep time, hence the thinner horizontal lines in the spectrogram. Secondly, beacon signals are not always detected with full signal strength; the strongest signal appears to be around −50 dBm, while the weakest yet still distinguishable signal is around −65 dBm. This is because when using the swept FFT mode, the sampling is not continuous and sometimes only part of the beacon packet is captured, leading to inaccurate power measurement. This observation is illustrated in Figure10, where the number of occurrences for the energy above various thresholds is plotted. In addition, the total number of sweeps in the recording is drawn as a reference. We observe that with the growth of spb, the probability of detecting a beacon signal with full signal strength increases. When the sampling time is larger than the beacon interval, in each buffer of samples, at least one complete beacon is captured; hence, all beacons that have been captured are displayed with correct signal strength. This observation reveals that for the swept FFT mode, there is a trade-off between the sensing efficiency and time resolution. It is obvious that decreasing the buffer size can improve the time resolution; however, at the same time, the channel switching time becomes more important compared to the total sweep time, which results in worse sensing efficiency.
We conclude that the swept FFT mode can effectively expand the frequency span, which helps give a global view of the spectrum. Despite the trade-off with the sensing efficiency, the time resolution can be conveniently configured using the spb parameter.
4.3 Bluetooth experiment
The Bluetooth technology utilizes frequency hopping spread spectrum modulation. There are 79 Bluetooth channels in the 2.4-GHz ISM band, and each channel has a 1-MHz bandwidth. A Bluetooth device hops to a different frequency every 625 μs. For the experiment, two nodes were paired with the Bluetooth interface. An unidirectional UDP traffic with 1-MB/s throughput is generated from the application layer on top of the Bluetooth stack. The Bluetooth activity was measured with a cooperative spectrum sensing system formed by four USRPs. Each USRP operates in the continuous FFT mode and covers 20 Bluetooth channels; as such, in total, a 80-MHz bandwidth is observed. All the nodes and USRPs have a line-of-sight connection.
To be able to assemble the spectrum from different USRPs into one complete spectrum covering all Bluetooth channels, we need to synchronize the system clock of the servers connected to the USRPs. This was achieved by using the Precision Time Protocol daemon (PTPd). PTPd allows computers within a local area network to keep their clock synchronized to a common clock source, commonly referred to as the master clock. In our system, the clock of server 1 is the master clock. After some time, the offset from master to slave starts to settle down to around 30 μs. As each Bluetooth packet occupies a random Bluetooth channel for 625 μs, the clock drifting is relatively small (5%) compared to the Bluetooth packet length, hence will allow us to identify the packets correctly.
The experiment is conducted via the OMF, where a central script is executed to make sure all USRP sensing engines start approximately at the same time. The time resolution is adjusted to 655 μs to better resolve the Bluetooth activity. Since all servers are synchronized to server 1, the timestamp from server 1 is used to derive the relative timestamp. The resulting spectrogram is shown in Figure11. It is possible to observe short 1-MHz-wide Bluetooth activities spread over the spectrum space. Additionally, it can be seen that there is no Bluetooth activity between 2,423 and 2,446 MHz. In recent implementations, Bluetooth does not necessarily use all the channels. As an example, the adaptive frequency hopping mechanism excludes channels with bad communication quality from the channel list.
In conclusion, this measurement demonstrates the possibility to form a distributed and cooperative sensing system with our sensing engine solution. The result can be used to identify Bluetooth activity in the wireless spectrum.
In this paper we first presented a brief survey of various spectrum sensing solutions. We argue that continuous spectrum sensing is important for channel occupation assessment. However, a sensing engine capable of continuous sensing with sufficient flexibility is still missing among today’s sensing solutions.
To close this gap, we developed a new sensing engine based on a commercial SDR platform. Compared to most low-cost sensing solutions, our solution provides much more flexibilities in terms of configuration. The most important feature is its capability of seamless capturing and long-term recording. The implementation is based on several open-source libraries supported on major platforms. This makes our solution transparent and being able to run on a broad range of operating systems. Additionally, our solution can easily be extended into cooperative and distributed sensing systems, as described in Section 4.3.
The solution we proposed relies on a standard PC for processing. On one hand, this makes it ideal for fast prototyping and development. On the other hand, it makes the solution less portable and not able to work in a stand-alone situation. How to migrate the software computational capability to an embedded platform is one of the remaining challenges. The basic idea is to shift the processing load from software to hardware. In this way, we do not require extensive processing power on an embedded system.
The pipelined software architecture and seamless spectrum sensing functionalities can be ported to an FPGA chip with minor effort; because independent hardware blocks works in parallel intrinsically. There exists a large amount of tools for translating software functionalities into hardware[31, 32], but attention should be paid to issues such as processing time, power consumption, etc. This is one of the ongoing activities for future extension.
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The research leading to these results has received funding from the European Union’s Seventh Framework Programme FP7/2007-2013 under grant agreement no. 258301 (CREW project).
The authors declare that they have no competing interests.
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Liu, W., Pareit, D., Poorter, E.D. et al. Advanced spectrum sensing with parallel processing based on software-defined radio. J Wireless Com Network 2013, 228 (2013). https://doi.org/10.1186/1687-1499-2013-228
- Fast Fourier Transform
- Cognitive Radio
- Spectrum Analyzer
- Sweep Time
- Clear Channel Assessment