# Two-dimensional DOA estimation of coherent sources using two parallel uniform linear arrays

- Heping Shi
^{1}, - Zhuo Li
^{2, 3}Email author, - Jihua Cao
^{4}and - Hua Chen
^{5}

**2017**:60

https://doi.org/10.1186/s13638-017-0844-0

© The Author(s). 2017

**Received: **14 November 2016

**Accepted: **20 March 2017

**Published: **31 March 2017

## Abstract

A novel two-dimensional (2-D) direction-of-arrival (DOA) estimation approach based on matrix reconstruction is proposed for coherent signals impinging on two parallel uniform linear arrays (ULAs). In the proposed algorithm, the coherency of incident signals is decorrelated through two equivalent covariance matrices, which are constructed by utilizing cross-correlation information of received data between the two parallel ULAs and the changing reference element. Then, the 2-D DOA estimation can be estimated by using eigenvalue decomposition (EVD) of the new constructed matrix. Compared with the previous works, the proposed algorithm can offer remarkably good estimation performance. In addition, the proposed algorithm can achieve automatic parameter pair-matching without additional computation. Simulation results demonstrate the effectiveness and efficiency of the proposed algorithm.

### Keywords

Matrices reconstruction 2-D DOA estimation Coherent signals Decoupled estimation Uniform linear array (ULA)## 1 Background

2-D direction-of-arrival (DOA) estimation of incident coherent source signals has received increasing attention in radar, sonar, and seismic exploration [1–5]. Many high-resolution techniques, such as MUSIC [6] and ESPRIT [7], have achieved exciting estimation performance. However, the aforementioned methods assume the incident signals are independent, which would encounter performance degradation due to the rank deficiency when coherent signals exist. To decorrelate coherent signals, the spatial smoothing (SS) [8] or forward-backward spatial smoothing (FBSS) [9] are especially noteworthy. However, this technique generally reduces the effective array aperture, and the maximum number of resolvable signals cannot exceed the number of array sensors. In [10], an effective matrix decomposition method utilizing cross-correlation matrix is proposed to decorrelate coherent signals. Chen et al. [11] have proposed a 2-D ESPRIT-like method that realizes decorrelation by reconstructing a Toeplitz matrix. With the help of three correlation matrices, Wang et al. [12] have presented a 2-D DOA estimation method. Recently, Nie et al. [13] have introduced an efficient subspace algorithm for 2-D DOA estimation. In [14], a novel 2-D DOA estimation method using a sparse L-shaped array is proposed to obtain high performance and less complexity. Xia et al. [15] have proposed a polynomial root-finding-based method for 2-D DOA estimation by using two parallel uniform linear arrays (ULAs), which has less computational burden. Some decorrelation algorithms are proposed in [16–18] to achieve 2-D DOA estimation by utilizing two parallel ULAs. However, the limitation of the abovementioned algorithms is that the estimation performance cannot be satisfactory due to the fact that the structure of the array is not being fully exploited.

For the purpose of description, the following notations are used. Boldface italic lower/uppercase letters denote vectors/matrices. (·)***, (·)^{T}, (·)^{†}, and (·)^{H} stand for the conjugation, transpose, Moore-Penrose pseudo-inverse, and conjugate transpose of a vector/matrix, respectively. The notation *E*(x) and *diag* (·) separately denote the expectation operator and the diagonal matrix, respectively.

## 2 Date model

_{ a }and Y

_{ a }) in the

*x*−

*y*plane. Each ULA has

*N*omnidirectional sensors with spacing

*d*

_{ x }, and the interelement spacing between the two ULAs is

*d*

_{ y }. Suppose that

*M*far-field narrowband coherent signals impinge on the two parallel ULAs from 2-D distinct directions (

*α*

_{ i },

*β*

_{ i })(1 ≤

*i*≤

*M*), where

*α*

_{ i }and

*β*

_{ i }are measured relatively to the

*x*axis and to the

*y*axis, respectively.

*k*th element of the subarray X

_{ a }be the phase reference and then the observed signals \( {x}_m^k(t) \) at the

*m*th element can be expressed as

*s*

_{ i }(

*t*) denotes the complex envelope of the

*i*th coherent signal,

*λ*is the signal wavelength, and

*d*

_{ x }represents the spacing between two adjacent sensors. The superscript

*k*(

*k*= 1, 2, ⋯,

*N*) of the \( {x}_m^k(t) \) stands for the number of the reference element in subarray X

_{ a }, and the subscript

*m*(

*m*= 1, 2, ⋯,

*N*) of the \( {x}_m^k(t) \) denotes the number of the element along the

*x*positive axis in subarray X

_{ a }.

*n*

_{ x,m }(

*t*) is the additive Gaussian white noise (AGWN) of the

*m*th element in subarray X

_{ a }.

*m*=

*k*, the observed signals at the

*k*th element can be expressed as

*k*th element of the subarray Y

_{ a }as the phase reference and then the observed signals \( {y}_m^k(t) \) at the

*m*th element can be expressed as

Similarly as in (1), the superscript *k*(*k* = 1, 2, ⋯, *N*) of the \( {y}_m^k(t) \) stands for the number of the reference element in subarray Y_{
a
}, and the subscript *m*(*m* = 1, 2, ⋯, *N*) of the \( {y}_m^k(t) \) denotes the number of the element along the *x* positive axis in subarray Y_{
a
}. *n*
_{
y,m
}(*t*) is the AGWN of the *m*th element in subarray Y_{
a
}
_{.}

**X**

^{ k }(

*t*) and

**Y**

^{ k }(

*t*) can be written as

## 3 The proposed algorithm

_{ a }, the auto-correlation calculation is defined as follows:

*k*th element of the subarray X

_{ a }is the phase reference. Thus, the auto-correlation vectors \( {\mathbf{r}}_{{\mathbf{X}}^k{\left({x}_k^k\right)}^{\ast}}^k \) between

**X**

^{ k }(

*t*) and the corresponding reference element \( {x}_k^k(t) \) can be defined as follows:

*N*column vectors will be achieved as the superscript

*k*of the \( {\mathbf{r}}_{{\mathbf{X}}^k{\left({x}_k^k\right)}^{\ast}}^k \) is changed from 1 to

*N*. Therefore, we construct an equivalent auto-covariance matrix

**R**

_{ xx }as follows:

_{ a }, the cross-correlation calculation \( {\tilde{r}}_{y_m^k{\left({x}_k^k\right)}^{\ast}}^k \) can be written as

**Y**

^{ k }(

*t*) and the reference element \( {x}_k^k(t) \) in subarray X

_{ a }can be expressed as

*N*column vectors when the superscript

*k*of the \( {\tilde{\mathbf{r}}}_{{\mathbf{Y}}^k{\left({x}_k^k\right)}^{\ast}}^k \) is varied from 1 to

*N*. Based on the

*N*column vectors, an equivalent cross-covariance matrix

**R**

_{ yx }can be given by

**R**

_{ xx }as in (10), we need to further investigate the auto-correlation calculation \( {r}_{x_m^k{\left({x}_k^k\right)}^{\ast}}^k \) in (6).

*m*th row of the steering matrix in covariance matrix with the scenario when the first element of the subarray X

_{ a }is set to be the reference element. According to (14), (15), and (16), Eq. (9) can be rewritten as

_{ a }, and \( \mathtt{a}\left({\alpha}_i\right)={\left[\begin{array}{cccc}\hfill 1\hfill & \hfill {e}^{- j\left(2\pi /\lambda \right){d}_x \cos {\alpha}_i}\hfill & \hfill \cdots \hfill & \hfill {e}^{- j\left(2\pi /\lambda \right)\left( N-1\right){d}_x \cos {\alpha}_i}\hfill \end{array}\right]}^T \).

**R**

_{ xx }in (10) can be rewritten as

*i*th element of the subarray X

_{ a }.

**R**

_{ xx }in (18), the equivalent cross-covariance matrix

**R**

_{ yx }in (13) can be rewritten as

From (18) and (19), it is easy to see that since *α*
_{
i
} ≠ *α*
_{
j
}, (*i* ≠ *j*), **A**(*α*) is a full column rank matrix with rank (**A**(*α*)) = *M*. Similarly, since *β*
_{
i
} ≠ *β*
_{
j
}, (*i* ≠ *j*), **Ψ**(*β*) is a full-rank diagonal matrix with rank (**Ψ**(*β*)) = *M*. According to (7) and (15), note that the incident signals *s*
_{
i
}(*t*) ≠ 0, (*i* = 1, 2 ⋯ *M*), so *g*
_{
i
}(*t*) ≠ 0. As a result, **G** is a full-rank diagonal matrix, namely, rank(**G**) = *M*. That is, if the narrowband far-field signals are statistically independent, the diagonal element *g*
_{
i
}(*t*) of the matrix **G** represents the power of the *i*th incident signal. If the narrowband far-field signals are fully coherent, the diagonal element *g*
_{
i
}(*t*) of the matrix **G** denotes the sum of the powers of the *M* incident signals. Notice that if the narrowband far-field signals are the coexistence of the uncorrelated and coherent signals, which means there are *K* coherent signals, the remaining are *M* − *K* statistically independent signals. Then, the diagonal element *g*
_{
i
}(*t*) of the matrix **G** stands for the sum of the powers of the *K* coherent signals when the subscript of the diagonal element *g*
_{
i
}(*t*) in matrix **G** corresponding to the source signal belongs to one of the *K* coherent signals. If the subscript of the diagonal element *g*
_{
i
}(*t*) in matrix **G** corresponding to the source signal belongs to one of the remaining *M* − *K* mutually independent signals, the diagonal element *g*
_{
i
}(*t*) of the matrix **G** denotes the power of the *i*th independent signal.

From the above theoretical analysis, the coherency of incident signals is decorrelated through matrices constructing no matter whether the signals are uncorrelated, coherent, or partially correlated.

*λ*

_{1}≥

*λ*

_{2}≥ ⋯ ≥

*λ*

_{ M }} and {

**U**

_{1},

**U**

_{2}, ⋯,

**U**

_{ M }} are the non-zero eigenvalues and eigenvector of the noiseless auto-covariance matrix \( {\widehat{\mathbf{R}}}_{xx} \), respectively. Then, the pseudo-inverse of \( {\widehat{\mathbf{R}}}_{xx} \) is

**A**(

*α*) is a column full-rank matrix, the Eq. (22) can be expressed as

**R**

_{ yx }can be rewritten as

**R**can be defined as follows:

Obviously, the columns of **A**(*α*) are the eigenvectors corresponding to the major diagonal elements of diagonal matrix **Ψ**(*β*). Therefore, by performing the EVD of **R**, the **A**(*α*) and **Ψ**(*β*) can be achieved. Then, the DOA estimation of the coherent signals can be achieved according to \( \upsilon \left({\beta}_i\right)={e}^{j\left(2\pi /\lambda \right){d}_y \cos {\beta}_i} \) and \( \mathtt{a}\left({\alpha}_i\right)={\left[1,{e}^{- j\left(2\pi /\lambda \right){d}_x \cos {\alpha}_i},\cdots, {e}^{- j\left(2\pi /\lambda \right)\left( N-1\right){d}_x \cos {\alpha}_i}\right]}^T \) without additional computations for parameter pair-matching and 2-D peak searching.

- (1)
Calculate the column vectors \( {\mathbf{r}}_{{\mathbf{X}}^k{\left({x}_k^k\right)}^{\ast}}^k \) of the equivalent auto-covariance matrix

**R**_{ xx }by (6) and (9). Similarly, compute the column vectors \( {\tilde{\mathbf{r}}}_{{\mathbf{Y}}^k{\left({x}_k^k\right)}^{\ast}}^k \) of the equivalent cross-covariance matrix**R**_{ yx }according to (11) and (12) - (2)
- (3)
Obtain the noiseless auto-covariance matrix \( {\widehat{\mathbf{R}}}_{xx} \) by (22). Then, perform EVD to obtain pseudo-inverse matrix \( {\mathbf{R}}_{xx}^{\dagger } \)

- (4)
Construct the new matrix

**R**by (29) and then get the**A**(*α*) and**Ψ**(*β*) by performing EVD of the new matrix**R** - (5)
Estimate the 2-D DOAs

**θ**_{ i }= (*α*_{ i },*β*_{ i }) of incident coherent source signals via \( \upsilon \left({\beta}_i\right)={e}^{j\left(2\pi /\lambda \right){d}_y \cos {\beta}_i} \) and \( \mathtt{a}\left({\alpha}_i\right)={\left[1,{e}^{- j\left(2\pi /\lambda \right){d}_x \cos {\alpha}_i},\cdots, {e}^{- j\left(2\pi /\lambda \right)\left( N-1\right){d}_x \cos {\alpha}_i}\right]}^T \).

## 4 Simulation result

*N*= 7 with sensor displacement

*d*

_{ x }=

*d*

_{ y }=

*λ*/2. Consider

*M*= 4 coherent signals with carrier frequency

*f*= 900MHz coming from

**α**= (75

^{o}, 100

^{o}, 120

^{o}, 60

^{o}) and

**β**= (65

^{o}, 75

^{o}, 90

^{o}, 50

^{o}). The phases of coherent signals are [

*π*/5,

*π*/3,

*π*/3,

*π*/3]. Results on each of the simulation are analyzed by 1000 Monte Carlo trials. Two performance indices, called the root-mean-square-error (RMSE) and normalized probability of success (NPS), are defined to evaluate the performance of the proposed algorithm and DMR-DOAM algorithm.

*α*

_{ n }and

*β*

_{ n }for the

*i*th Monte Carlo trial respectively, and

*K*is the source number.

*ϒ*

_{suc}and

*Τ*

_{total}denote the times of success and Monte Carlo trial, respectively. Furthermore, a successful experiment is that satisfies \( \max \left(\left|{\widehat{\theta}}_n-{\theta}_n\right|\right)<\varepsilon \), and

*ε*equals 0.5 for estimation of the coherent signals.

*α*or the RMSE curve of the

*β*. Fig. 3 shows the NPS of the DOAs versus SNR, which illustrates that the performance of the proposed algorithm is better than that of the DMR-DOAM algorithm. Furthermore, even at low SNR, the proposed algorithm can still achieve better estimation performance. The reason is that the proposed algorithm takes full advantage of all the received data of the two parallel ULAs to construct the equivalent auto-covariance matrix

**R**

_{ xx }and cross-covariance matrix

**R**

_{ yx }, which can improve the estimation precision. On the contrary, the DMR-DOAM algorithm obtains the DOAs of signals at the cost of reduction in array aperture, which often leads to poorer DOA estimation.

*ρ*is varied from 0 to 1 between

*s*

_{1}(

*t*) and

*s*

_{2}(

*t*). The SNR is set at 5 dB, and the number of snapshots is 800. Note that the

*ε*in (32) is set to be 0.6 in this simulation. The performance curves of the DOA estimation against correlation factor are shown in Figs. 6 and 7. From Figs. 6 and 7, we can see that the proposed algorithm outperforms the DMR-DOAM algorithm.

## 5 Conclusions

A novel decoupling algorithm for 2-D DOA estimation with two parallel ULAs has been presented. In the proposed algorithm, two equivalent covariance matrices are reconstructed to achieve the decorrelation of the coherent signals and the estimated angle parameters are pair-matched automatically. It has been shown that the proposed algorithm yields remarkably better estimation performance than the DMR-DOAM algorithm.

## Declarations

### Acknowledgements

This research was supported by the National Natural Science Foundation of China (61602346), by the Key Talents Project for Tianjin University of Technology and Education (TUTE) (KYQD16001), by the Tianjin Municipal Science and Technology innovation platform, intelligent transportation coordination control technology service platform (16PTGCCX00150), and by the National Natural Science Foundation of China (61601494).

### Competing interests

The authors declare that they have no competing interests.

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## Authors’ Affiliations

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