Smart antenna with automatic beam switching for mobile communication

Abstract

A new kind of smart antenna capable of automatically switching its main beam to track a moving target is presented. The antenna, which is suitable for mobile communication in long straight spaces, such as railways or highways, integrates a sensing element, signal processing element, and radiating element. The sensing element works based on a frequency-modulated continuous wave and delivers a beat frequency signal containing environmental information to the signal processing element, which is used to control the excitation of the radiating element. To verify the efficiency of the proposed antenna, a prototype is fabricated and implemented in a real corridor scenario. Furthermore, the error vector magnitude (EVM) along the test path is investigated to evaluate the system performance when using the proposed antenna. The results show that this kind of smart antenna is capable of improving mobile communication quality and decreasing energy consumption. Therefore, it is a promising candidate for mobile communication.

1 Introduction

With the development of electronic technology and the advent of mobile communication, the construction of flexible and variable short-range wireless communication channels for environmental adaptability has become an important task in the design of mobile communication systems, in which antennas play a key role. For such systems, low-cost antennas may not always be emphasized, but more likely, in the case of moderate cost, antennas have flexible and intelligent characteristics and are combined with artificial intelligence to achieve environmentally cognitive intelligence. Such smart antennas can reduce the energy consumption and increase the reliability of wireless communications.

The concept of smart antennas has existed for many years and has received wide attention [1]. Many kinds of antennas have found potential applications in smart communication and detection systems. In [2], an antenna with the capability of radiation pattern changing between six states in the azimuth plane, which is controlled by p-i-n diodes, is proposed. In [3], a compact electronically steerable passive array with six folded monopoles that can realize frequency-controlled scanning by using varactors is proposed. In [4], a smart antenna with beam switching capability that can realize beam switching between 0, 90, 180, and 270° by means of diodes is presented.

In [5], a smart antenna with beam and polarization switching capabilities in the azimuth plane is proposed. In [6], a two-dimensional scanning smart antenna for cognitive radio is proposed. In [7], a graphene antenna with dynamic control of the radiation pattern by means of setting specific chemical potentials based on graphene is presented. In [8], a smart antenna array with different types and nonuniform distributed elements that can process multiple signals at multiple frequencies simultaneously is proposed. In [9], a shape changeable parabolic smart antenna is designed to transmit a signal with a given gain to desired positions by controlling the shape of the antenna using a shape-memory alloy. In [10], a smart antenna system with interference mitigation capability that is realized by generating radiation nulls in the interferer direction is presented. In [11], a novel reconfigurable adaptive linear array is proposed for finding the optimal radiation direction in which the spatial correlation coefficient is minimal, and in [12], the antenna is further formed to minimize the spatial correlation coefficient. In [13], a neural network-based smart antenna is proposed for multiple source tracking. In [14], a beam-steering reconfigurable antenna for automatically searching for the maximum receiving signal power is proposed. In [15], a beam tracking scheme in the downlink of 5G cellular radio access that can choose candidate beams based on mobility-reference signals is proposed. However, although these antennas have potential applications in smart mobile communication systems, external control systems must be used, and the antennas themselves do not have the function of automatic sensing and adjusting their characteristics according to environmental information. Therefore, these antennas cannot be seen as the real “smart” antennas.

The smart antenna proposed in this paper itself has a target distance sensing function, the capability to process sensed target data, and the ability to automatically make judgments and switch its beams. All these functions of sensing, data processing and automatic switching are integrated into a single smart antenna. Although the antenna is not as small as fractal antennas [16] [17], it can be easily placed on a ceiling. It works similarly to the human eye and always keeps the target in an optimum radio link state. The method and experiment are introduced in Section II. The design scheme and prototype of the antenna are presented in Section III, and the performance of the antenna is verified by measurement in Section IV. Finally, conclusions are drawn in Section V.

2 Method and experiment

First, the constitution of the smart antenna is given. The principle and structure of each element are presented, and the integration of all elements is demonstrated. The experiment is based on numerical simulations and measurements. The radiating element is simulated and measured. In addition, to verify the effectiveness of the proposed antenna, the properties of the smart antenna are tested in a real corridor. The analysis shows that the proposed antenna is useful and effective for mobile communication.

2.1 Antenna description

A human-eye-like antenna has the capability of perceiving environmental changes and making corresponding adjustments during operation. Similar to the human eye, when the antenna detects a variation in distance from a target, the radiation pattern of the antenna will immediately change to track the target and keep the target in the focus region of the antenna. Theoretically, the radiation pattern of the antenna must be changed continuously by the beam scanning technique. However, for simplicity, the radiation pattern is changed only by switching excitation between three different radiating sub-elements in this paper.

2.2 Antenna configuration

The antenna proposed in this paper consists of three integrated parts, that is, the sensing element, signal processing element, and radiating element, as shown in Fig. 1. The sensing element can be acoustic, electronic or any other kind of environment sensor: in this paper, two 24 GHz frequency-modulated continuous wave (FMCW) distance sensors are used. The signal processing element extracts distance information of targets from the output signal of the sensors, and in this paper, Texas Instruments model TMS320F28335 are used. The radiating element transmits and receives the RF signal to and from the desired directions: two Yagi-Uda antennas and one patch antenna are integrated to construct the radiating element. When the proposed antenna is in operation, excitation can be automatically switched between the three radiating subelements in accordance with the presupposed trigger positions of vehicles. The mobile communication system only sends an RF signal to the antenna as usual; the antenna itself automatically establishes and changes the wireless communication channel in real time and keeps the channel in the optimum state.

Fig. 1

Operation diagram of the smart antenna

2.3 Sensing element

In the sensing element, two CFK024-5A FMCW distance sensors are used [18]; the sensors work at 24 GHz with dimensions of 25 mm ⋅ 25 mm ⋅ 6 mm. The sensing element is powered by a 5 V DC source and is stimulated by a triangle wave. The outputs of the sensors are beat frequency signals obtained by mixing the transmitting and receiving signals, from which distance information of the targets can be obtained [18]. The radiators on the sensors have beamwidths of 80 and 32° in the horizontal and vertical planes, respectively, and the output RF power can reach 15 dBm. The sensors work based on frequency-modulated waves, and the sensing distance R is given by [19]:

$$ R= fdcT/2B $$

(1)

where f_d is the frequency of the beat frequency signal, B and T are the sweep bandwidth and duration, respectively, and c denotes the velocity of light. Notably, B is determined by a voltage-controlled oscillator (VCO), which is excited by a triangle wave with a repeat frequency of 80 Hz, as illustrated in Fig. 2. The amplitude variation range of the triangular wave is set from 0.1 to 1.8 V, corresponding to a sweep bandwidth of 150 MHz (23.25–24.75 GHz). Figure 2 also shows the amplified output signal of the sensors, which contains the beat frequency signal, as shown by the ripple wave superimposed on the triangle wave. Notably, the frequency of the sweep wave is linearly correlated with the instantaneous amplitude of the frequency-modulated wave (triangle wave). For example, when the value of the modulation signal is 0.1 V, the frequency of the sweep wave is 23.25 GHz. When the modulation signal increases, the frequency of the sweep wave also increases and reaches its peak at 24.75 GHz (corresponding to 1.8 V). Hence, the beat frequency signal is extracted from the transmitting and receiving signals (reflected from the targets) by a mixer during every scanning period, as illustrated in Fig. 3. Therefore, future work will focus on how to obtain f_d. Additionally, the Doppler effect should be considered when a vehicle is traveling at high speed. For the proposed antenna, the Doppler effect is similar to that of the commonly used base-station antenna with relatively high gain. When seen from different elements of the proposed antenna, the Doppler effect of the two Yagi elements is larger than that of the patch antenna.

Fig. 2

Modulation signal (blue line) and amplified output signal (yellow line) from the FMCW distance sensor, whose prototype is shown in the bottom-right corner. The photo was obtained from an oscilloscope

Fig. 3

Block diagram of the FMCW distance sensor

2.4 Signal processing element

As mentioned above, the beat frequency signal is a time-domain waveform. Therefore, a signal processing circuit should be designed to process the analog signal before analog-to-digital conversion (ADC), which includes a two-stage preamplifier, an active fourth-order high-pass filter, a single-stage amplifier and a booster circuit (the ADC can only receive signals greater than 0), as shown in Fig. 4. Note that the beat frequency signal determined by the target distance ranges from approximately 500 Hz to approximately 3 kHz in this paper, which is superimposed on the frequency-modulated wave (80 Hz) as the output signal of the sensors shown in Fig. 3. To obtain the beat frequency signal, we removed the triangle wave using an active fourth-order high-pass filter with a stop band less than 500 Hz. By means of ADC, with a sampling rate of 781.25 KHz integrated on a DSP of type TMS320F28335, we obtain the digital beat frequency signal. To further obtain the frequency of the digital beat frequency signal and the corresponding distances of targets, DFT is considered. To reduce the consumption of computational resources and time, methods with low computational cost, such as FFT or the modified fractional derivative of the Riemann ζ function, should be used [20]. Here, a 128-point FFT unit is adopted, which is expressed by

$$ X(k)=\sum \limits_{n=0}^{\frac{N}{2}-1}{x}_1(n){W}_{N/2}^{kn}+{W}_N^k\sum \limits_{n=0}^{\frac{N}{2}-1}{x}_2(n){W}_{N/2}^{kn} $$

(2)

Fig. 4

Analog signal processing circuit. a Two-stage preamplifier. b Active fourth-order high-pass filter. c Single-stage amplifier and booster circuit

where x(n) = x₁(n) + x₂(n), N = 128, and x₁(n) and x₂(n) are even and odd sequences, respectively. In this way, the numbers of calculations can be reduced to (N/2)log₂N for multiplication and Nlog₂N for addition.

2.5 Radiating element

The radiating element consists of two Yagi-Uda antennas [21] for endfire coverage and one patch antenna [22] for broadside coverage, as shown in Fig. 5. The antennas are designed on a Rogers 6010 substrate with ε_r = 10.2 and tanδ = 0.0023εr=10.2tanδ=0.0023 and share the same ground plane with sizes of 161.14 mm × 119.00 mm × 0.635 mm¡mm×119.00mm×0.635mm. The distance between the antennas is set to 42.05 mm to reduce coupling. The two Yagi-Uda antennas are located at two opposite edges of the substrate, while the patch antenna is located at the middle of the substrate. With this design, the radiation beams of the antennas can cover zones of 1, 2, and 3 simultaneously or separately by exciting the corresponding antennas, as shown in Fig. 1. The parameters of the antennas are given in Table 1, and the radiating element is simulated using CST. Fig. 6 shows the fabricated radiating element.

Fig. 5

Structure of the radiating element. a Details of the Yagi-Uda antennas. b Schematic of the radiating element with details of the patch antenna, SE1-SE3 denote radiating sub-elements

Table 1 Parameters of the proposed radiating element

Fig. 6

Photographs of the radiating element. a TTop view. b Bottom view

2.6 Setup of the smart antenna

As illustrated in Fig. 7, the sensing element, signal processing element, and radiating element are integrated to construct the smart antenna. An FR4 printed circuit board (PCB) with an overall size of 110.00 mm × 85.00 mm × 1.75 mmnmm×85.00mm×1.75m, which contains a signal processing circuit and DSP, is fixed on the back of the ground plane of the antenna, sandwiching a foam layer with a thickness of 8 mm. The diffraction effect to the PCB from radiating elements can be overlooked [23, 24]. The circuit is powered by a 12 V DC source. The ground plane of the antenna has a size of 119.00 mm × 117.20 mmwmm, and it plays a role in screening the interference from the circuit behind. The two FMCW distance sensors powered by the PCB are installed on the substrate edge of the antenna at opposite edges and are placed as far as possible away from the antenna input terminal to reduce their influence. In addition, the sensors are installed on two small rotatable holders. Once the trigger positions and the distances between the antenna and targets are given, we can rotate the sensors to the appropriate positions to improve the detection accuracy. The proposed smart antenna is sufficiently lightweight to be readily mounted on the ceiling, as shown in Fig. 8.

Fig. 7

Prototype of the smart antenna. a Top view. b Front view. c Side view

Fig. 8

Illustration of the mounting of the smart antenna

Notably, although the proposed antenna is capable of tracking multiple targets simultaneously by exciting all or several radiating elements, for simplicity, this paper focuses on the case where only one target is tracked, and only one antenna is excited at a time to illustrate the efficiency of the smart antenna.

The operation principle of the proposed antenna is shown in Fig. 9. The procedure of beam switching between different regions is illustrated in Fig. 5 and Fig. 7. When the antenna is in operation, the sensors are active, and when sensor 1 receives a signal from a vehicle, for example, the left Yagi-Uda antenna (sub-element 1) radiates a wave to zone 1. When the vehicle moves to the presupposed position (closer to the antenna), the signal processing element generates a signal and sends it to the switch to automatically realize an excitation handover between the left Yagi-Uda antenna and the middle patch antenna, and the radiation area is changed from zone 1 to zone 2. Here, switches with RS14-SN12T18 SP4T are used to control the on-off status of the input ports of the three radiating sub-elements. Identically, when the vehicle moves towards the right direction and is far from the smart antenna, the right Yagi-Uda antenna (radiating sub-element 3) is excited, and zone 3 will become the illuminating area as soon as the vehicle reaches the second trigger position. The antenna in this paper is proposed mainly for applications in long straight spaces, such as subways or corridors. The two beams of the Yagi-Uda antennas with higher gain point to the two ends of the long straight space and cover the regions far from the smart antenna, as denoted by zones 1 and 3 in Fig. 1, while the beam from the patch antenna covers the region near the antenna, as denoted by zone 2 in Fig. 1.

Fig. 9

Principle block diagram of the smart antenna. FDS and SPC denote the FMCW distance sensor and signal processing circuit, respectively

3 Results and discussion

Measurement systems, including measurements in a microwave chamber and in a realistic scenario, were established to verify the efficiency of the proposed smart antenna.

3.1 Radiation characteristics

The S-parameters of the proposed antenna were measured first by an Agilent E8363C PNA network analyzer, and the results are shown in Fig. 10. Note that sub-elements 1, 2, and 3 correspond to the three antennas. It can be seen from Fig. 10 that the measured bandwidths of the two Yagi-Uda antennas are 9.49% (5.22–5.74 GHz) and 9.21% (5.28–5.72 GHz), respectively, and are relatively wider than that of the patch antenna, which is only 0.36% (5.60–5.62 GHz). The bandwidth of the patch antenna can be improved by using aperture-coupled feeding [22], which will be done in our future work. The isolation between the radiating sub-elements is greater than 38 dB. Theoretically, S11 and S33 should be close to each other, and S12 and S21 should be the same. The deviations in Fig. 10 may be caused by the fabrication tolerance and the measurement environment. In addition, because the values of S12 and S21 are very small and sensitive to the environment, if the antenna is moved slightly during measurement of S21 and S12, the two values will be different.

Fig. 10

Measured S-parameters of the three radiating subelements

Figure 11 shows the measured radiation patterns of the sub-elements. The E-planes of sub-element 1 and sub-element 3 in Fig. 11a correspond to the x–y plane shown in Fig. 5, whereas the E-plane of sub-element 2 corresponds to the y–z plane, and the angles in the figures are counted from the +z direction. Figure 11b shows the radiation patterns in the H-plane (x–z plane) of the three sub-elements. To facilitate observation, the radiation directions of the three elements are oriented to 90, 180, and 270°, corresponding to the −x, −z, and +x directions, respectively. The measured gains of sub-elements 1 to 3 at 5.61 GHz are 5.34 dBm, 2.24 dBm, and 4.94 dBm, respectively, and their normalized cross polarization levels are − 34.18 dB, − 40.91 dB and − 29.54 dB.

Fig. 11

Measured radiation patterns of the three radiating sub-elements of the smart antenna at 5.61 GHz. a E-plane. b H-plane

3.2 Performance of the smart antenna

The radiation performance of the proposed antenna was measured in a real scenario of a long straight corridor in a large building. The corridor is 1.75 m in width and 2.4 m in height. Before measurement, the two sensors on the antenna were tested to obtain their effective sensing range. The relationship between the target distance and beat frequency signal is shown in Fig. 12, from which we can see that the sensing distance changes almost linearly with the beat frequency signal. Here, it is worth noting that the relationship between the target distance and beat frequency signal is considered basic knowledge and is deposited into the DSP before the measurement of the whole antenna system

Fig. 12

Measured relationship between trigger position and beat frequency signal

The setup of the measurement system is shown in Fig. 13. The received level along the corridor was measured by an Agilent FieldFox RF Analyzer N9912A. The proposed antenna was suspended at a height of 1.9 m at the midpoint of the corridor in the horizontal direction. It was used as the transmitting antenna and was fed by an R&S SMB100A signal generator with an operating frequency of 5.61 GHz. The receiving antenna was an omnidirectional antenna fixed on an antenna platform at a height of 1.35 m. It was connected to the analyzer, and the analyzer was further connected to a computer to record the measurement data. During the measurement, the receiving terminal moved straight along the corridor at a constant speed, and the computer sampled the data in real time.

Fig. 13

Setup of receiving level measurement of the smart antenna

Figure 14 gives the distributions of the received power for the cases of exciting only one sub-element at a time during the test and for the case of exciting the appropriate sub-element in terms of the target position by means of automatic switching. As seen in Fig. 14a, when sub-element 1 is excited, the received power in zone 1 is higher than that in zone 3 and reaches its maximum at approximately − 1.3 m. When sub-element 2 is excited, the peak of received power occurs at the zero position and attenuates gradually along both the +x and −x directions, as shown in Fig. 14b. Sub-element 3 has the same radiation characteristics as sub-element 1 but points in the opposite direction, so the received power curve is symmetric to that of sub-element 1, as shown in Fig. 14c. Here, we set the trigger distances to +0.7 m and − 0.7 m to obtain a relatively smooth level reception. From the curve in Fig. 14d, we can see that when the proposed antenna is working in the mode of automatically switching between sub-elements in terms of the trigger distances, as expected, a relatively smother distribution of receiving power can be obtained.

Fig. 14

Distributions of the received power for the transmitting antenna operating in different modes, (a), (b) and (c) are the curves measured along the whole path when only one subelement is excited at a time (without switching), (d) is the curve measured when the antenna is operated in the mode of automatic switching in terms of trigger distance

We obtained different distributions of receiving power by changing the trigger distances, as illustrated in Fig. 15. For clarity and simplicity, we only show the power distributions on a half measurement path. As shown by the curve in Fig. 15a, for which the trigger distance was set to − 2 m, the received power gradually increased when the receiving antenna moved from – 8 m towards the +x direction. The increasing trend is denoted by a dashed line. In this case, a conspicuous drop occurs at approximately – 2 m, and the received power decreases below the dashed line before the receiving antenna reaches the switching position. The trends of the receiving power for other trigger distances are similar to that of – 2 m. The only difference is the dropping position, which occurs at – 3 m, − 4 m, and – 5 m. Notably, for the trigger distance of − 5 m, the receiving power decreases more slowly from − 1.2 m to – 5 m. The main reason is that the measurement environment is a corridor, which is a kind of confined space, and the waveguide effect can affect the propagation property, which is unlike that in free space.

Fig. 15

Measured receiving power when the trigger position is set to a− 2 m, b – 3 m, c− 4 m, and d − 5 m, as indicated by black arrows

To further validate the performance, the proposed antenna was applied to a wireless communication system to investigate the communication quality, as shown in Fig. 16. In the system, a pair of YunSDR Y320 baseband modules (comprising a generator, encoder and decoder) and quadrature phase-shift keying (QPSK) modulation mode were used to perform the measurement. In the transmitting terminal, a Y320 was connected to a computer to receive orders and data. The processed data frames with a bandwidth of 20 Mbps were modulated on a carrier frequency at 5.61 GHz and were continuously sent to the proposed antenna via an RF switch. After starting, the data frames propagating in the wireless channel were received by the receiving antenna. Finally, the data sent by the first computer were obtained by another computer.

Fig. 16

Block diagram of the EVM measurement setup

In this part of the measurement, the error vector magnitude (EVM) [25], an index to evaluate the performance of the whole system, was tested, with a sampling interval of 0.2 m along the measurement path. The EVM is expressed by

$$ \mathrm{EVM}=\sqrt{\frac{P_{\mathrm{error}}}{P_{\mathrm{reference}}}}\times 100\% $$

(3)

where P_error is the average power of the error vector and P_reference is the average power of the reference signal.

The results are shown in Fig. 17. The trigger positions were set at – 1 m and + 1 m, which means that the range of zone 1 is from – 8 m to −1 m, and the ranges of zones 2 and 3 are from – 1 m to 1 m, and from 1 m to 8 m, respectively. The performance of the whole system was tested for individual sub-elements without switching and for the case of automatic switching between sub-elements in terms of trigger distance. The results are shown in Fig. 17a–d. When the three sub-elements are excited individually, as the three curves in Fig. 17a–c show, small-scale fluctuation can be observed in the range of 60%, which is caused mainly by intersymbol interference on account of the multipath effect in the tested corridor. On the other hand, considering zone 1, when only sub-element 1 is excited, the maximum value of EVM is approximately 60% at − 7.1 m. When only sub-element 2 or 3 is excited, as shown by the curves in Fig. 17b, c, respectively, most of the EVM is located in the upper half of the figures, namely, above 50%, even exceeding 100% at − 7.4 m when only sub-element 3 is excited. In zone 2, the curves in Fig. 17a, c show that the EVM is not stable near the two trigger boundaries. However, when sub-element 2 is active, the EVM exhibits optimal performance in zone 2. The structure of sub-element 3 is identical to that of sub-element 1, so it performs best in zone 3. Furthermore, in zones 1 and 3, each curve in Fig. 17a–c has a lower envelope, which can be used to adjust the performance of the radiating sub-elements more explicitly. In Fig. 17e, the envelopes of the radiating sub-elements in zone 1 are fitted out. The EVM derived from the signal received by sub-element 1 is the lowest, while the EVMs for subelements 2 and 3 are higher. However, in zone 3, sub-element 3 is the best choice of the three sub-elements. Figure 17e, f are not symmetric because the impacts of the testing environment are asymmetric, as shown in Fig. 13. In addition, the time variation of the wireless channel is also an influencing factor. The curve in Fig. 17d shows the case of trigger positions at − 1 and 1 m, from which it can be seen that the lower envelope of EVM remains relatively lower in zones 1 and 3 compared to those in the three curves in Fig. 17a–c, and the EVM in zone 2 is more stable and lower, which means that the proposed antenna guarantees the communication quality of the wireless communication system. In this paper, we show only the results measured in a confined space, but our design can also be extended to mobile communication in open spaces such as highways or railways.

Fig. 17

Distributions of EVM for a transmitting antenna operating in different modes. The three curves in a, b, and c were measured along the whole path when only one element was excited at a time (without switching). The curve in d was measured when the antenna was operated in the mode of automatic switching in terms of trigger distance. e Lower envelope of EVM of the curves in a, b, and c in zone 1. f\ Lower envelope of EVM of the three curves in a, b, and c in zone 3

4 Conclusion

This paper presents a new kind of smart antenna with the capability of automatic beam switching and low complexity. The antenna consists of sensing, signal processing, and radiating elements. In the sensing element, two 24 GHz radar sensors based on FMCW are used to detect the distances of targets. A signal processing circuit is designed to extract the beat frequency signal from the output of the sensors. In the radiating element, two Yagi-Uda antennas for endfire radiation and one patch antenna for broadside radiation are designed on a Rogers 6010 substrate with the same polarization and overlapping working frequency band. To verify the performance of the proposed antenna, measurements in a long corridor were performed. The results show that the communication quality can be improved by the smart antenna, which could be used for vehicles to facilitate future mobile communication.