Fast Signal Recovery in the Presence of Mutual Coupling Based on New 2-D Direct Data Domain Approach

Adaptive antenna arrays are strongly affected by the existence of mutual coupling (MC) effect between antenna elements; thus, if the effects of MC are ignored, the system performance will not be accurate [1, 2]. Research into compensation for the MC has been mainly based on the idea of using open circuit voltages, firstly proposed by Gupta and Ksienski [2]. While this method has calculated the mutual impedance, the presence of other antenna elements has been ignored and a very simplified current distribution has been assumed for each antenna elements. Many efforts have been made to compensate for the MC effect for uniform linear array (ULA) and uniform circular array (UCA) [2–9]. In [3], an adaptive algorithm was used to compensate for the MC effect in a ULA. In [7], the authors introduced a minimum norm technique MC compensation method, which is based on the technique in [2] for general arrays with arbitrary elements and more accurate. In [9], a new method was proposed to compensate for the MC effect which relied on the calculation of a new definition of mutual impedance. however, the authors did not deal with 2-D DOA estimation problem.

On the other hand, many algorithms of the 1-D DOA estimation have been extended to solve the 2-D cases [10, 11]; however, a few have considered the effect of mutual coupling or any other array errors [12]. Besides, most of these proposed adaptive algorithms are based on the covariance matrix of the interference. However, these statistical algorithms suffer from two major drawbacks. First, they require independent identically-distributed secondary data in order to estimate the covariance matrix of the interference. Unfortunately, the statistics of the interference may fluctuate rapidly over a short distance, limiting the availability of homogeneous secondary data. The resulting errors in the covariance matrix reduce the ability to suppress the interference. The second drawback is that the estimation of the covariance matrix requires the storage and processing of the secondary data. This is computationally intensive, requiring many calculations in real-time. Recently, direct data domain algorithms have been proposed to overcome these drawbacks of statistical techniques [13–16]. The approach is to adaptively minimize the interference power while maintaining the array gain in the direction of the signal. The sample support problem is eliminated by avoiding the estimation of a covariance matrix which leads to enormous savings in the required real-time computations. The performance of this algorithm is affected by the MC effect, too [17] and must be compensated.

Unfortunately, the MC matrix tends to change with time due to environmental factors, so full elimination of its effect and prediction of its variability are impossible. Therefore, calibration procedures based upon signal processing algorithms are needed to estimate and compensate for the effect of the MC. The most likely way is to carry out some measurements for calibration. However, this procedure has the drawbacks of being time-consuming and very expensive [18]. Some other researches suggested self-calibration adaptive algorithms for damping the MC effect [19–21].

In this paper, a new adaptive algorithm was proposed for the fast recovery of the signal with one snapshot of receiving signals in the presence of mutual coupling, based on 2-D D³LS algorithm for URA. Then, utilizing the 2-D D³LS algorithm properties, a novel technique for the coupling coefficients estimation, without using any auxiliary sensors is presented.

This paper is organized as follows. Section 2, conventional 2-D D³LS algorithm is reviewed. In Section 3, a fast adaptive algorithm of direct data domain including mutual coupling effect is presented. In Section 4, a new technique is presented for compensation of the MC effect. In Section 5, numerical simulations illustrate these proposed techniques which can accurately recover the desired signal in the presence of MC.

If one assumes that denotes the mutual coupling matrix (MCM) of the array, the output will be as:

(10)

(11)

Svantesson [6] showed that the coupling between the neighboring elements with the same interspace is almost the same and the magnitude of the mutual coupling coefficient between two far apart elements is so small that can be approximated to zero. Thus, a banded symmetric Toeplitz matrix can be used as a model for the mutual coupling of ULA and URA. In this paper, each sensor is assumed to be affected by the coupling of the 8 sensors around it, which is shown in Figure 2.

We define MCM as [12]:

(12)

where and are submatrices of and can be given by

(13)

Then, the following equation is derived to recover the desired signal in the presence of mutual coupling (Proof in the appendix), notwithstanding to compute the inverse matrix of MC. Hence, this equation could be reduced the computation of the algorithm

(14)

where is the weights vector when coupling is known and

(15)

The conventional recovering of the signal is as the following:

(16)

where denotes, rows from the vector. is computationally intensive and requires many calculations in the real-time because evaluation of the inverse requires an process (here denotes "on the order of"). Therefore, (14) can be replaced with (16) and the number of processes would be an .

In this section, a new method is presented to estimate the coupling coefficients from the properties of the 2-D D³LS algorithm. If the mutual coupling effect is ignored, the term , for and will have no signal components. However, in the presence of MC, for the edge elements in the URA, the above term can be written as the following:

(17)

As is seen in (17), when there are no interferers, the equations can be solved. In this paper, it is assumed that ; so . The above equations can be solved in order to estimate , , and . Once the system estimates the coupling coefficient, it needs only one snapshot of the data in order to obtain an acceptable solution. So, when the coupling is unknown, first we can estimate mutual coupling from (17) and then, the fast recovering of the signal is as the following:

(18)

where is the estimation of and is with replacement of , , with , , .

In this section, the capability of MC compensation for the proposed algorithm will be tested with two examples. Consider a URA with elements in which the spacing between each two elements in rows and columns is . The array receives the desired signal with one jammer. The signal to noise ratio is 20 dB and other parameters are listed in Table 1.

	Magnitude	Phase
Signal	1–10 V/m	0	75°	45°
Jammer1	1000 V/m	0	43°	−77°

The number of adaptive weights chosen for our simulation will be 16 [16]. Jammer is 60 dB stronger than the intensity of the desired signal. The magnitude of incident signal varies from 1 V/m to 10 V/m; but jammer intensities are constant as given in Table 1. Figure 3 shows the accuracy of the recovered signal in the presence of MC using new formulation (18) with comparison to the ideal recovering. Figure 4 shows the result of the recovered signal in the presence of MC, using a new proposed algorithm with comparison to the ideal recovering. The expected linear relationship is clearly seen and the jammer has been nulled and signal recovered correctly.

Later on, the performance of the proposed method is illustrated by the various simulations. The amplitude of the desired signal accuracy is measured by the root mean-squared error (RMSE), and is the number of Monte Carlo runs.

Figure 5 shows the RMSE of the estimated coupling coefficients versus signal-to-noise ratio (SNR). Figure 6 shows the RMSE of the estimated amplitude of the desired signal, versus SNR. For high SNR, error is very low and in case there is no noise, new formulation is equal to the ideal.

In this paper, the problems of 2-D D³LS algorithms were studied for recovering of the signal in the presence of mutual coupling and driving a new formulation to recover the signal in the presence of MC. Without using the moment of method and impedance matrix calculation, coupling coefficients can be automatically estimated and without computing the inverse matrix, the desired signal can be recovered. Because we did not use the inverse MC matrix, the amount of computation would be reduced. Moreover, simulation results were confirmed when SNR was high and the RMSE of the method was very close to the ideal D³LS in the absence of MC.

In this appendix, (8) and (14) are proved. Consider a URA consisting of elements. The array receives one signal from a known direction and one interferer (this proof can be extended similarly). From (1), let the received signal at the array in the presence of mutual coupling for each element be

(A.1)

where , are the received signal and jammer at the th element, expressed as

(A.2)

By taking mutual coupling into account, from (11) for each column

(A.3)

(a) Absence of the Mutual Coupling

If the one row from each column is multiplied by and subtracted from the next row and then the result of each column is multiplied by and subtracted from the next column, in the absence of mutual coupling, this will cancel out all the signals and only noise and interferer will be left

(A.4)

The weight vectors should be in a way that produces zero output; therefore, a reduced rank matrix is formed in which the weighted sum of all its elements would be zero. In order to make the matrix not singular, the additional equation is introduced through the constraint that the same weights when operating on the signal produced a gain factor , which is the first equation. Therefore, (5) will be

(A.5)

(A.6)

Then, performing the matrix multiplication in (A.6) for the first row of the matrix will give

(A.7)

With performing the matrix multiplication in (A.6) for the second row of the matrix the following is obtained:

(A.8)

So

(A.9)

, , and , (A.9) will be true for all if and only if each summation in the parenthesis is equal to zero. Therefore, the first summation will be used

(A.10)

Similarly, the same can be done for the third row of the matrix (A.5), and so forth. In the absence of mutual coupling . From (A.3) and (A.10)

(A.11)

Then, (A.11) will be as simple as

(A.12)

Therefore, the desired signal can be recovered by

(A.13)

(b) Presence of the Mutual Coupling

When there is mutual coupling, the matrix (A.5) can be formed and the (A.3) and (A.10) can be written in a similar way

(A.14)

Similar to (A.11), the following can be presented

(A.15)

The recovered signal will be as follows:

(A.16)