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Adaptive CSI and feedback estimation in LTE and beyond: a Gaussian process regression approach

  • 1, 2Email author,
  • 3,
  • 1,
  • 1, 2 and
  • 1, 2
EURASIP Journal on Wireless Communications and Networking20152015:168

https://doi.org/10.1186/s13638-015-0388-0

  • Received: 20 December 2014
  • Accepted: 14 May 2015
  • Published:

Abstract

The constant increase in wireless handheld devices and the prospect of billions of connected machines has compelled the research community to investigate different technologies which are able to deliver high data rates, lower latency and better reliability and quality of experience to mobile users. One of the problems, usually overlooked by the research community, is that more connected devices require proportionally more signalling overhead. Particularly, acquiring users’ channel state information is necessary in order for the base station to assign frequency resources. Estimating this channel information with full resolution in frequency and in time is generally impossible, and thus, methods have to be implemented in order to reduce the overhead. In this paper, we propose a channel quality estimation method based on the concept of Gaussian process regression to predict users’ channel states for varying user mobility profiles. Furthermore, we present a dual-control technique to determine which is the most appropriate prediction time for each user in order to keep the packet loss rate below a pre-defined threshold. The proposed method makes use of active learning and the exploration-exploitation paradigm, which allow the controller to choose autonomously the next sampling point in time so that the exploration of the control space is limited while still reaching an optimal performance. Extensive simulation results, carried out in an LTE-A simulator, show that the proposed channel prediction method is able to provide consistent gain, in terms of packet loss rate, for users with low and average mobility, while its efficacy is reduced for high-velocity users. The proposed dual-control technique is then applied, and its impact on the users’ packet loss is analysed in a multicell network with proportional fair and maximum throughput scheduling mechanisms. Remarkably, it is shown that the presented approach allows for a reduction of the overall channel quality signalling by over 90 % while keeping the packet loss below 5 % with maximum throughput schedulers, as well as signalling reduction of 60 % with proportional fair scheduling.

Keywords

  • 5G
  • Channel state information
  • OFDMA
  • Signalling overhead
  • LTE
  • Dual control
  • Active learning

1 Introduction

Future cellular networks are envisioned to provide extremely high quality of service to an ever increasing number of interconnected users [1]. Many technologies are currently being explored in order to evolve from current 4G networks to future 5G communication. One aspect that has yet to be fully addressed is the signalling overhead imposed on a network with billions of connected devices [24]. The control information overhead is, in fact, still a very relevant problem for 4G cellular networks, such as long term evolution (LTE). Future 5G networks will, most likely, make use of the same radio access technology utilised by LTE: orthogonal frequency division multiple access (OFDMA). In this work, we present techniques to predict and minimise a user’s packet loss by means of limiting the control information in the time domain for a downlink OFDMA network. The simulations are carried out in an LTE environment as this is the most advanced cellular network available today but the methods presented and the results achieved can be easily generalised for future 5G scenarios. In LTE, OFDMA divides the bandwidth into orthogonal blocks, called physical resource blocks (PRBs), and a frequency domain scheduler assigns such PRBs to the served users based on their channel conditions [5]. In order to provide each user with the highest quality of service, the base stations employ adaptive modulation and coding (AMC) techniques which adjust different modulation and coding schemes (MCS) used for transmission according to the channel state information (CSI) signals fed back from the users. Therefore, relevant and timely CSI signalling is extremely important to allocate the wireless resources to the users and maximise the overall network capacity. Full CSI feedback (FB), although optimal in maximising the downlink capacity, cannot be used in LTE as the standard quantises both the amount of channel state information the users feed back in the frequency domain as well as how often this information can be reported in time [6].

In [7], we have shown that it is possible to limit channel state information, in frequency, without loss in performance if the freed uplink bandwidth is allocated for payload communication. We have also shown that the number of served users under different fairness strategies, imposed by the frequency resource allocation mechanisms, influence the impact of FB allocation strategies and that it is possible to determine the optimal FB allocation. The impact of FB information is then a function of the number of users served by the base station, their channel quality and the scheduling algorithm used to assign the PRBs. In this work, we show that it is possible to compensate for the capacity loss due to reducing the CSI signalling in time, even with already quantised frequency resolution, via the usage of per-user channel quality prediction and per-user dynamic assignment of prediction time windows.

Considerable work has been devoted by the research community to either channel quality prediction or feedback overhead reduction. In [8], the authors implement and compare various signal-to-interference-and-noise ratio (SINR) prediction algorithms and conclude that high gains can be expected when using covariance-based predictors for low mobility users. In [9], the authors present a prediction method used to compensate for CSI delay. The estimation is performed at the mobile user side and the predictor takes into account the Doppler shift of each user for more accurate estimation. Both works make use of the users’ Doppler shift to determine the time duration of the channel quality estimation; this procedure, although well established, might lead to erroneous predictions, a negative correlation is generally present between prediction quality and Doppler shift. On the other hand, a high mobility user might witness a better, less variable channel than a low mobility user. Furthermore, users have to predict the SINR themselves, depleting their battery life. In [10], the authors propose a dynamic Channel Quality Index (CQI) allocation method, which is a quantised value indicative of the SINR experienced by the users and predicted at the base station. The CQI allocation time of each user is adapted based on the instantaneous packet loss of each user. In [11], the same authors expand their results by including CQI prediction at the base station. They use a linear predictor and compensate for errors by reducing or increasing the prediction windows based on the users’ packet loss. In [12], the authors present a nonpredictive signalling reduction scheme where only users with low SINR are allowed to feed back expensive instantaneous CQI information while high SINR users only transmit wideband information. Even though the method decreases the signalling information, it is carried out for a limited and fixed time window (2 ms) and a single cell scenario, ignoring the underlying network dynamics due to interference, traffic load, etc.

The main objectives of this work are twofold. Firstly, we propose an online and adaptive CQI prediction scheme to estimate users’ channel quality variations at the base station side, while compensating for some of the quantization noise introduced by sampling the SINR at certain CQI values. The proposed CSI estimation approach is based on Gaussian process regression which has been shown to be efficient in the presence of noisy measurements [13]. Gaussian processes (GPs) are also used to estimate the distribution of variables rather than their values, making them attractive for solid predictions over noisy datasets. Furthermore, GPs provide a principled framework in which their parameters can be estimated with maximum likelihood techniques removing constraints related to the fine-tuning of such predictors [14].

Secondly, we leverage the GP-based prediction mechanism for the CQI assignment problem, in which a base station controller is able to monitor the behaviour of each served user and assign a personalised prediction time window based on that user’s performance and requirements. For this procedure, a dual-control system based on active learning, as introduced in [15], is used. The dual controller is able to monitor and predict the base station’s performance and assign a time window to each user based on specific requirements. The active learning component is used to limit the amount of necessary data sampling before an optimal policy is reached. In order to demonstrate the effectiveness of the proposed methods, we consider a multi-user, multi-cell LTE network. The quality of the GPR for CQI prediction is presented for different user speeds, and afterwards, simulation results for the dual-control system are shown for both proportional fair and maximum throughput scheduling.

This paper is structured as follows: Section 2.1 introduces the considered system model, the standard-compliant CSI allocation strategies and the resource allocation mechanisms used throughout this work. In Section 3, the prediction model used to estimate the users’ channel quality is presented. In Section 4, the online dual-control mechanism is proposed to determine dynamically the optimal prediction window for a given user. In Section 5, the performance of the proposed solutions is presented. Finally, in Section 6, the concluding remarks are drawn.

2 System model

2.1 Network model

The network is composed of B base stations (eNBs), each serving an equal amount N U of mobile users (MUs). LTE makes use of time-frequency resource allocation, in which the frequency bandwidth is split into orthogonal units called physical resource blocks, each of which is allocated separately. For each PRB k an MU measures its received SINR, defined as:
$$ \gamma_{k} = \frac{P_{i,k}G_{i,k}}{\sum_{j \neq i} P_{j,k}G_{j,k} + n_{k}} $$
(1)

where P i and G i are the transmit power and transmission gains of the serving base station i while P j and G j are the transmit power and transmission gains of the interfering base stations j and n k is the additive Gaussian noise.

Even though the PRB is the smallest unit, the base station can allocate to each user; in order to limit the amount of signalling information, each MU is unable to feed back detailed information on each PRB, and thus the PRBs are generally grouped in subbands and only one value for such band is measured. This value is referred to as the effective SINR and is computed with the Effective Exponential SNR Mapping (EESM) formulation [16]:
$$ \gamma_{eff} = - \lambda \log \left(\frac{1}{N} {\sum_{s}^{S}} \exp^{-\frac{\gamma_{s}}{\lambda}} \right) $$
(2)
where S represents the size of the subband and λ is a parameter empirically calibrated by the base station. The effective SINR is then quantised into a channel quality indicator (CQI) value, indicative of the highest modulation and code rate the base station may use while keeping a packet error rate (PER) below a target of 10 % as shown in Table 1 [17]. Each user then feeds back these CQI values to the base station.
Table 1

SINR and CQI mapping to modulation and coding rate

SINR

CQI

Modulation

Code rate

Efficiency

   

(× 1024)

(information bits per symbol)

−6.9360

1

QPSK

78

0.1523

−5.1470

2

QPSK

120

0.2344

−3.1800

3

QPSK

193

0.3770

−1.2530

4

QPSK

308

0.6016

0.7610

5

QPSK

449

0.8770

2.6990

6

QPSK

602

1.1758

4.6940

7

16QAM

378

1.4766

6.5250

8

16QAM

490

1.9141

8.5730

9

16QAM

616

2.4063

10.3660

10

64QAM

466

2.7305

12.2890

11

64QAM

567

3.3223

14.1730

12

64QAM

666

3.9023

15.8880

13

64QAM

772

4.5234

17.8140

14

64QAM

873

5.1152

19.8290

15

64QAM

948

5.5547

Once the eNB has collected the CQIs for the entire bandwidth, it schedules resources for each user according to its resource allocation function.

2.2 LTE feedback schemes

2.2.1 2.2.1 “Frequency domain feedback”

In a practical scenario, the CQI reporting is not performed for each PRB but it is quantised in frequency to reduce the control signalling overhead. The three reporting techniques used in the LTE standard are presented in [6].
  • Wideband: each user transmits a single 4-bit CQI value for all the PRBs in the bandwidth.

  • Higher Layer configured or subband level: the bandwidth is divided into q subbands of S consecutive PRBs and each user feeds back to the base station a 4-bit wideband CQI and a 2-bit differential CQI for each subband. The value of k is bandwidth dependent and is given in Table 2, where \(N_{\textit {PRB}}^{DL}\) is the total number of downlink PRBs in the bandwidth (table 7.2.1-2 in [6]).
    Table 2

    Subband size (S) vs. system bandwidth for subband level feedback

    System bandwidth

    Subband size

    \(N_{\textit {PRB}}^{DL}\)

    (S)

    6–7

    NA

    8–10

    4

    11–26

    4

    27–63

    6

    64–110

    8

  • User-selected, or Best-M: each user selects M preferred subbands of equal size S and transmits to the base station one 4-bit wideband CQI and a single 2-bit CQI value that reflects the channel quality over the selected M subbands. Additionally, the user reports the position of the selected subbands using P FB bits, where P FB , as given in [6], is:
    $$ P_{FB} = \left\lceil log_{2} {N_{PRB}^{DL} \choose M} \right\rceil \;, $$
    (3)
    where \({N_{\textit {PRB}}^{DL} \choose M}\) is the binomial coefficient. The value of M and the amount of PRBs in each subband are given in Table 3 (table 7.2.1-5 in [6]):
    Table 3

    Subband size (S) and number of subbands (M) vs. system bandwidth for user-selected feedback

    System bandwidth

    Subband size

    M

    \(N_{\textit {PRB}}^{DL}\)

    (S)

     

    6–7

    NA

    NA

    8–10

    2

    1

    11–26

    2

    3

    27–63

    3

    5

    64–110

    4

    6

Amongst the three standard compliant feedback schemes, only the subband level technique allows the base station to investigate the channel quality of the complete bandwidth with equal amount of detail between subbands. For this reason, it has been chosen, in this work, as the preferred FB method and the GPR process is aided by the constant resolution over the bandwidth. Furthermore, excluding the wideband FB, which does not allow frequency selective scheduling, it is the least expensive in terms of uplink bandwidth, Table 4 includes the mathematical definitions of the bit cost of the different feedback allocation methods presented in Section 2 when the standard code rate of \(\frac {1}{2}\) is used. Figure 1 shows the amount of feedback required for the different schemes as a function of the number of users with a 20 MHz (100 PRBs) UL bandwidth using QPSK modulation (the horizontal line represents the total uplink bandwidth).
Fig. 1
Fig. 1

Portion of uplink PRBs used for CSI feedback. This figure shows how much of the uplink bandwidth is allocated to channel quality signalling if full feedback or standard compliant feedback schemes are used

Table 4

Bit cost of the frequency selective standard complaint FB methods

Feedback scheme

Bit cost

Wideband

2·(4·N U )

Subband level

2·(4+2·qN U

User-selected

\(2 \cdot (4 + 2 +\lceil log_{2} {N_{\tiny {PRB}}^{\tiny {DL}} \choose \tiny {M}} \rceil)\cdot N_{U} \)

2.2.2 2.2.2 “Time domain feedback”

The CSI is limited in the time domain. The periodicity of CQI reporting is determined by the base station, and the CQI signalling is divided into periodic and aperiodic reporting [18]. In case of aperiodic CQI signalling, the eNB specifically instructs each user on which frequency granularity to use and when the reporting has to occur. With aperiodic reporting, the eNB can make use of any of the CQI standard compliant feedback methods discussed above. Periodic CQI reporting, on the other hand, is more limited and only wideband and user-selected feedback methods can be used. In this case, the CQI messages are transmitted to the base station with constant periodicity, e.g. in case of periodic wideband feedback in an FDD system, each user can report its CQI values every 2, 5, 10, 16, 20, 32, 40, 64, 80 and 160 ms. For the remainder of this work, we assume that an aperiodic feedback is used, as this allows the eNB controller to adapt the CQI transmission time more freely than with periodic reporting.

2.3 Resource allocation mechanisms

While the CQI information defines the achievable rate on each PRB, the overall cell transmission rate is a function of the resource allocation mechanism implemented at the base station. Two scheduling methods are used in this work to define the impact of CQI prediction and assignment on the cell throughput:
  • Best CQI (BCQI), or max-rate, is a greedy scheduler designed to maximise the cell throughput. For each PRB, only the user with the highest channel quality indicator is scheduled.

  • Proportional Fair (PF): this scheduler is designed to aim for high throughput while maintaining fairness amongst users. PF schedules users when they are at their peak rates relative to their own average rates, at a given time instant t, PF schedules user \(x_{i} = \arg \max \frac {r_{i,k}(t)}{R_{i}(t)}\), where r i,k (t) is the instantaneous data rate of user x i on PRB k at time t and R i (t) is the average throughput, computed with moving time window T, such that \(R_{i}(t) = \frac {1}{T}\sum _{j= t-T}^{t} r_{i}(j)\).

3 CQI prediction

We now turn our attention to the description of the CQI estimation methods. The estimation process is carried out to compensate for the reduction in CQI reporting in time. Given the relationship between CQI and SINR described in Section 2.1, predicting the CQI is equivalent to predicting a noisy function of the relative effective SINR. Due to the Gaussian nature of the SINR distribution and the inherent flexibility of Gaussian Processes for regression, these have been selected in this work.

3.1 Gaussian process regression

The objective of GPR is to estimate a function f in an online manner with low complexity. A Gaussian process (GP) is defined as a probability distribution over some variables, where any finite subset of these variables forms a joint Gaussian distribution [19]. This means that, instead of making assumptions on the elements of a dataset, a GP infers their distribution. Let us consider a dataset D={x i ,,y i } with i=1,2,…n, where each x i and y i represent the input and output points. We define the relation between such vectors as y=f(x)+n, where n is a zero-mean Gaussian noise with variance σ 2. A GP is defined as a collection of random variables, such that any finite set has a joint Gaussian distribution. Since a Gaussian distribution is completely defined by its mean and covariance matrix, a GP is completely defined by its mean function m(x) and covariance function \(k(\boldsymbol {x},\boldsymbol {\tilde {x}})\), expressed as:
$$ f(\boldsymbol{x)} \thicksim GP(m(\boldsymbol{x}),k(\boldsymbol{x},\boldsymbol{\tilde{x}})), $$
(4)
where
$$ \begin{array}{lcl} m(\boldsymbol{x}) & = & \mathbb{E}[f(\boldsymbol{x})] \\ k(\boldsymbol{x},\boldsymbol{\tilde{x}}) & = & \mathbb{E}[(f(\boldsymbol{x}) - m(\boldsymbol{x}))(f(\boldsymbol{\tilde{x}}) - m(\boldsymbol{\tilde{x}}))]. \end{array} $$
(5)
The output can be defined by a GP, such that:
$$ y \thicksim GP(m(\boldsymbol{x}),k(\boldsymbol{x},\boldsymbol{\tilde{x}}) + \sigma^{2} \boldsymbol{I}) \;, $$
(6)
By aggregating the inputs into a vector X and the outputs into a vector Y, the GP estimates the value of \(\hat {y}\) at a future point x , assuming a multi-variate distribution:
$$ \left[ \begin{array}{c} \boldsymbol{Y} \\ \hat{y} \end{array} \right] \thicksim N \left(\left[\begin{array}{c} m \\ m_{*} \end{array} \right], \left[\begin{array}{cc} K(\boldsymbol{X},\boldsymbol{X}) + \sigma^{2}\boldsymbol{I} & K(\boldsymbol{X},x_{*}) \\ K(\boldsymbol{X},x_{*}) & k(x_{*},x_{*}) \end{array} \right]\right) $$
(7)
where K(X,X) is the matrix representation of the covariance functions of the input samples and K(X,x ) is the covariance matrix of the overall input dataset and k(x ,x ) is the autocorrelation of the future data point. The posterior probability \(\hat {y}|\boldsymbol {Y}\) is given by [13]:
$$ \begin{aligned} \hat{y}|\boldsymbol{Y} \thicksim &\, N \left(K(\boldsymbol{X},x_{*})\left[K(\boldsymbol{X}, \boldsymbol{X}) + {\sigma_{n}^{2}}\boldsymbol{I}\right]^{-1}\boldsymbol{Y}, \; k(x_{*},x_{*}) \right.\\&\left.-\, K(\boldsymbol{X},x_{*})\left[K(\boldsymbol{X},\boldsymbol{X})+ {\sigma_{n}^{2}}\boldsymbol{I}\right]^{-1}K(\boldsymbol{X},x_{*})^{T} \right), \end{aligned} $$
(8)

The best estimate for \(\hat {y}\) is given by the mean of such distribution \(m(\boldsymbol {\hat {Y}}) = K(\boldsymbol {X},x_{*})\left [K(\boldsymbol {X},\boldsymbol {X})+ {\sigma _{n}^{2}}\boldsymbol {I}\right ]^{-1}\boldsymbol {Y}\) and the variance \(Var(\boldsymbol {\hat {Y}}) = k(x_{*},x_{*}) - K(\boldsymbol {X},x_{*}) \left [K(\boldsymbol {X},\boldsymbol {X})+ {\sigma _{n}^{2}}\boldsymbol {I}\right ]^{-1}K(\boldsymbol {X},x_{*})^{T}\) represents the uncertainty of the current estimate. The GP is then fully defined by its covariance and mean functions and their parameters.

3.2 Covariance function selection

In order to obtain a good estimate of the future measure and its underlying distribution, a covariance function that best fits the nature of the system has to be selected. As the mean can easily be set to zero if some pre-processing is carried out, it is usually ignored [13]. Although the covariance function K is limited to positive semi-definite functions, many choices are present in literature able to fit to dynamic, time-varying systems [19]. The most important feature when choosing a covariance function is its smoothness, i.e. how much the value of the function sampled at a point x correlates with the same function at points close to x . A function that presents high smoothness might not be representative of a fast-varying system. It could be possible, in theory, to observe a large realisation of an input dataset and generate a specific covariance function which models the witnessed behaviour very closely. This is normally not performed as a few families of covariance functions are present in literature which adapt quite well to a large selection of problems in which the data can be modelled as a multivariate Gaussian distribution [13]. For this reason, in the current task of modelling, the channel quality for users with varying mobility a Matérn class covariance function has been selected [20]:
$$ k(x,x_{*}) = h^{2} \frac{2^{1-v}}{\Gamma(v)} \left(\sqrt{2v} \left| \frac{x - x_{*}}{w} \right| \right) \mathcal{K}_{v} \left(\sqrt{2v}\left| \frac{x - x_{*}}{w} \right| \right), $$
(9)
where \(\mathcal {K}_{v}\) is the modified Bessel function. The Matérn covariance functions, such as the one selected in this work, include both the exponential autocorrelation (if the smoothness is equal to \(\frac {1}{2}\)) and the Gaussian autocorrelation (with infinite smoothness). These conditions make the Matérn class of covariance functions very flexible as they are able to strike a balance between the two extremes [21]. The variables h, v and w are defined as hyperparameters of the covariance function. They determine the shape of the covariance function and have to be fine-tuned in order for the GP to converge to an appropriate solution. By increasing the smoothness hyperparameter v, the function becomes smoother in time and fast variations of datapoints are ignored. By increasing the width hyperparameter w, the covariance function considers a wider set of datapoints, and by increasing the height hyperparameter h, larger variations in datapoints values are allowed. Once the covariance function is selected, the following step is to determine the values of the hyperparameters. This is performed by maximising the marginal likelihood of the Gaussian process. Since GPR is a form of Bayesian regression, the marginal likelihood is equal to the integral over the product of the prior and the likelihood function. Since both are Gaussian, the marginal likelihood is also Gaussian and is expressed in analytical form:
$$ \begin{aligned} p\left(\boldsymbol{Y}| \boldsymbol{X}, \theta, \sigma^{2}\right) & = \int p(\boldsymbol{Y}| f, \boldsymbol{X}, \theta, \sigma^{2}) p(f| \boldsymbol{X}, \theta)df \\ & = \int \mathcal{N}(f, \sigma^{2},\boldsymbol{I}) \mathcal{N}(0,\boldsymbol{K})df \\ & = \frac{1}{(2\pi)^{\frac{n}{2}}|\boldsymbol{K} + \sigma^{2}\boldsymbol{I}|^{\frac{1}{2}}}\\ &\quad\exp\left(-\frac{1}{2}y^{T}\left(\boldsymbol{K} + \sigma^{2}\boldsymbol{I}\right)^{-1}y\right) \end{aligned} $$
(10)
Where θ is the set of hyperparameters. Generally speaking, for simplicity, the log marginal likelihood is maximised [13]:
$$\begin{array}{*{20}l} \log p\left(\boldsymbol{Y}|\boldsymbol{X}, \theta\right) =& - \frac{1}{2} \boldsymbol{Y}^{T} (K + {\sigma_{n}^{2}}\boldsymbol{I})^{-1}\boldsymbol{Y}\\& - \frac{1}{2} \log|K + {\sigma_{n}^{2}}\boldsymbol{I}| - \frac{n}{2} \log2\pi. \end{array} $$
(11)

By using any multivariate optimization algorithm, the set of hyperparameters θ can be estimated analytically. After the optimization process has reached the analytical solution, the numerical values of the hyperparameters are simply obtained by using the measured input and output signals. This is a great advantage over other types of regression as it allows the system to evolve without pre-specifying the parameters and thus limiting the range of estimations [22].

3.3 GPR for CQI prediction

In this work, the eNB makes use of GPR to predict the CQIs values for every subband seen by each user. In order to make realistic predictions, the output vector Y is used to train the GP. For each user, the base station receives the CQI information for the complete bandwidth, using the subband-level FB quantization scheme discussed in Section 2.2 every t samp =2m s. The value of the sampling window t samp is chosen as the minimum allowed by LTE standard to acquire a high number of samples in a short time [23]. After the observation time elapses, say at instant t 0, the eNB uses GPR to predict the future CQI values in each subband as shown in Algorithm 1.

4 Dynamic time window optimisation

In this section, we introduce a control mechanism to determine the appropriate duration of the CQI prediction window so that the eNB can maintain each user’s performance within a specified loss margin. Firstly, the dual-control system based on active learning is introduced and, secondly, its implementation in an LTE base station for time windows optimisation is presented.

4.1 Dual control with active learning

A dual-control agent is tasked with controlling a system based on the current knowledge of its behaviour and to perturb it in order to minimise the uncertainty and make better predictions. By their nature, these objectives are conflicting. In this work, we follow the adaptive dual-control method proposed in [15], which provides a solution to the control problem while also limiting the amount of overhead.

Let us define a dynamic, non-linear, partially observable d-dimensional system described by:
$$ y_{j}(t+1) = h_{j} \left(y(t),c(t)\right) + n(t) \; \; \; \; \; \; \text{with} \; \; \; j = 1 \cdots d, $$
(12)
where y j (t+1) is the value of the output system at time t+1, which is function of the system behaviour h(·) given the past observation y(t) and the control function c(t). n(t) is a zero-mean Gaussian noise. In this context, h(·) corresponds to the function to be estimated (f), according to the formalism of the previous section. Given a d-dimensional reference signal r(t), the dual-control problem consists in finding the best control strategy μ(t) such that
$$ \mu(t) = \arg \min_{c(t)} \left\lVert y(t) - r(t) \right\rVert, \;\;\; \forall{t} $$
(13)
Furthermore, it is possible to limit the amount of data collected by the controller by maximising the information collected. If \(\hat {h}\) is an estimate of the system dynamics h based on previous observations, the dual control with active learning problem consists in finding the optimal strategy μ(t) solving the following optimisation problem:
$$ \max_{u(t)} \mathfrak{I}(\hat{h},c(t)) \approx \arg \min_{c(t)} Var(\hat{h},c(t)) $$
(14)
where \(\mathfrak {I}\) represents the Shannon information of the dynamic system and Var is the variance [15]. The objectives of the active dual controller consist in partially identifying the dynamics of the system so that it can be kept as close as possible to the reference signal while sampling only in the points that minimise uncertainty for future predictions. Figure 2 presents a block description of the dual-control framework.
Fig. 2
Fig. 2

Dual control with active learning framework. Block diagram of the proposed dual control with an active learning method

The dual control with active learning can be formally described as (Proposition 4 in [15]): Let the input-output relationship of a discrete-time dynamic system be defined as in Equation 12.

Let \(\hat {h}\) be the predicted estimate of the system’s behaviour, in this case, the packet loss due to reducing the time sampling of CQI values. The predicted future value \(\hat {y}(t+1)\) can be inferred as:
$$ \hat{y}(t+1) = \hat{h} \left(y(t),c(t)\right) + n(t). $$
(15)
The optimal strategy μ is then defined as
$$ \mu(t) = \arg \min_{c(t)} w_{a} \left\lVert \hat{y}(t+1) - r(t) \right\rVert - w_{e} {Var}(\hat{y}(t+1),c(t)) $$
(16)

where w a and w e represent the action and exploration weights to steer the controller towards either steepest descent to the closest optimal solution (w e =0) or to a complete exploratory behaviour (w a =0). Generally, the weights can be adjusted so that the controller behaves more exploratory at the beginning of the learning procedure and then moves to a more active controlling role.

4.2 Dual control for signalling reduction

In the dual-control framework for dynamic time window optimisation, we make use of the same GPR used for CQI prediction. In this case, the GPR is used to predict the packet losses each user incurs when different time windows are chosen. At time t 0, the eNB receives the CQI FB from each user u, then it chooses a time prediction window \(t_{w_{u}}(t_{0})\) and uses GPR to predict the CQI behaviour for the duration of such window. At the same time, it uses GPR to predict the packet loss \(\hat {L_{u}}(t_{0} + 1, t_{w_{u}}(t_{0}))\) the user will experience given the current time window. The objective of the controller is then to solve, for every user u:
$$ \begin{aligned} t_{w_{u}}(t+1) =&\, \arg \min w_{a,u} \left\lVert \hat{L_{u}}(t+1) - r_{u,th} \right\rVert\\ &- w_{e,u} Var(\hat{L_{u}}(t+1),t_{w_{u}}(t)), \end{aligned} $$
(17)

where r u,t h is the reference packet loss for user u. At time \(\phantom {\dot {i}\!}t_{0} + t_{w_{u}}(t_{0})\), the eNB measures the actual packet loss suffered by the user. The controller then corrects the CQI prediction window accordingly to provide better predictions and the process is repeated. Algorithm 2 provides a concise view of the solution above.

5 Results

In this section, we will first define the simulation environment and then provide the results for the proposed models.

5.1 Simulation parameters

The system has been simulated using the open source VIENNA system level simulator [24]. An urban multi-cell environment has been considered to include the effects of multipath propagation and interference; 19 LTE macrocells are simulated with 30 users per cell, in which only the users in the most central cell are studied to reduce border effects. In order to model the effects of user mobility in a city-like environment, the users have an average speed of 5, 10 or 60 km/h. The propagation model is deterministic and based on the Winner Channel Model II [25]. The simulation parameters are included in Table 5.
Table 5

System parameters

Parameters

Values

Number of macrocells

19

Sectors per macrocell

3

Inter-cell distance

500 m

Macro antenna gain

15 dB

Macro transmit power

46 dBm

Macro users per sector

2 to 100

Frequency

2.1 GHz

System bandwidth

20 MHz

Number of PRBs

100

Access technology

OFDMA FDD

Number of antennae

1(Tx and Rx)

Channel model

Winner Channel Model II [25]

Block fading mean

0 dB

Block fading deviation

10 dB

Fast fading

10 dB

Thermal noise density

−174 dBm/Hz

Users speed

5 to 60 km/h

5.2 Simulation results

Firstly, we present the impact that the various frequency sampling schemes of Section 2.2 have on the packet loss experienced by users. The CQI FB messages are sampled at specific moments in time, and the previously sampled value is used until the next sampling moment. Figure 3 shows the normalised goodput of a user moving at 10 km/h when the full feedback, subband-level, best-M and wideband schemes are employed.
Fig. 3
Fig. 3

Goodput loss of CQI FB frequency schemes over sampling times. This figure shows the goodput of a user whether the full feedback or the standard compliant frequency selective feedback methods are used and the CQI sampling time is increased

It is visible that there is a loss in goodput when either the CSI frequency sampling methods are used or the CSI sampling time interval is increased. On the other hand, the effects of increasing the duration between sampling instants are less pronounced when the CQI information is quantised in frequency. This is particularly visible for the wideband FB scheme, where the initial goodput is just above one third of the full feedback but the loss in time is almost null. For large time sampling intervals, the three standard compliant FB schemes behave better than the full feedback. For the remainder of this work, the subband level method is employed, as it presents, for almost all the sampling delays considered, the highest gain amongst the standard compliant schemes.

The effects of GPR CQI prediction for fixed CQI time sampling are presented in Figs. 4, 5 and 6 for users with speeds of 5, 10 and 60 km/h. The figures show the average packet loss seen by a user when either prediction or fixed time sampling is used. By fixed sampling, we intend that the base station only uses the last received CQI value until a new one is sampled. For the first two plots, the GPR CQI prediction shows considerable gains over the alternative.
Fig. 4
Fig. 4

Packet loss for user moving at 5 km/h over time sampling intervals. This figure shows the packet loss experienced by a user moving at 5 km/h when GPR prediction or CQI averaging are used

Fig. 5
Fig. 5

Packet loss for user moving at 10 km/h over time sampling intervals. This figure shows the packet loss experienced by a user moving at 10 km/h when GPR prediction or CQI averaging are used

Fig. 6
Fig. 6

Packet loss for user moving at 60 km/h over time sampling intervals. This figure shows the packet loss experienced by a user moving at 60 km/h when GPR prediction or CQI averaging are used

When users operate in high mobility, such as in Fig. 6, the prediction remains valid only for a very small time duration. This is due to the fact that the fast varying channel does not allow for reliable estimation for extended time intervals. Nonetheless, it is possible to exploit the GPR estimation’s gain over the sampling if short time windows are used.

Figure 7 shows an example of the estimated and real CQI values for a user moving at 10 km/h with a prediction window of 10 ms. There is good accordance between the predicted CQIs and the real values. The GPR is able to model the changes in the user’s channel.
Fig. 7
Fig. 7

Estimated and real CQI values. The figure shows the actual measured and the predicted CQI values for a user moving at 10 km/h

Figure 8 shows the root mean square error (RMSE) of the GPR predictions for different training datasets. In case of users moving at 5 and 10 km/h, we can see that convergence is reached and a large observation window allows the GPR to make an accurate estimation. When users have high mobility, on the other hand, a large training can lead to more errors as the time correlation of the CQI values decreases as seen in Fig. 8 c.
Fig. 8
Fig. 8

RMSE for various observation windows and user mobility. This figure shows the computed RMSE when the training window for the GPR is varied for users moving at 5, 10 and 60 km/h. a User speed 5 km/h, b user speed 10 km/h and c user speed 60 km/h

The impact of different covariance functions on the CQI estimation process with GPR is presented in Fig. 9. The Matérn function with smoothness \(v=\frac {3}{2}\) behaves best. A detailed analysis of the various functions in the figure can be found in [13].
Fig. 9
Fig. 9

RMSE of different covariance functions. Comparison of the error committed when different covariance functions are used for the GPR

By using the dual-control scheme, it is possible to set a maximum limit to the user’s packet loss due to limited time feedback. If a user is selected to be scheduled by the eNB, then a predicted packet loss can be inferred with the proposed model and a decision is made based on Equation 17. In order to analyse a dynamic scenario, users with diverse requirements are simulated together; a total of 60 users are served within the cell, of which 30 have low mobility (5 km/h), 20 have average mobility (10 km/h) and 10 are high speed users (60 km/h). Table 6 shows the percentage of FB required by the system for various packet loss threshold values for both the proportional fair and best CQI schedulers after the model has converged to the optimal decision compared to the state of the art where no prediction is used and the CSI is sampled every 2 ms. There are considerable gains for both schedulers but, as the PF maximises fairness, every user will be scheduled in the upcoming time slots and thus the time windows have to be inferred so that the predicted packet loss is minimised. On the other hand, since the dual-control model has as input the packet loss of each user, if such user is not scheduled, then the loss is null and a higher time window can be selected. For this reason the best CQI scheduler allows for much higher gains with an almost 94 % reduction in FB signalling when the allowed packet loss is contained to only 5 %.
Table 6

Percentage FB necessary with dual control

PL threshold

FB amount needed [%]

[%]

Proportional fair

Best CQI

5

40

6.2

10

23

4

20

9.7

3.3

30

6.3

3.3

Figure 10 presents the behaviour of the proposed dual-control method in Algorithm 2 for a single user. The packet loss at the sampling instants is indicated with the X markers while the square markers indicate the average sampled packet loss. The proposed solution then gradually builds a predicted packet loss behaviour, indicated in Fig. 10 by the continuous curve. At each iteration, the model selects the next time window according to (17) with weights w a =1 and w e =10 and predicts the packet loss behaviour for the duration of the selected window. After the time window has passed, the eNB samples the packet loss again, corrects its prediction and determines the next prediction time window until it converges to the desired packet loss threshold. In this specific realisation, the packet loss threshold is imposed at 10 % and the optimal inferred time window is 5 ms. It is important to notice that, because of the time varying nature of the channel, the measured loss can oscillate even if the time windows’ sampling is kept constant. The GPR takes this into account as measurement noise and is still able to approximate the system dynamics.
Fig. 10
Fig. 10

Predicted packet loss and measurements for different prediction time windows. This figure shows the predicted and measured packet loss for various time windows. The figure also shows the final action taken by the controller in order to keep the packet loss below a 10 % threshold

Figure 11 a, b shows the prediction error calculated at each iteration and the variance of the prediction model; in both cases, the proposed approach reaches the desired behaviour after only five iterations.
Fig. 11
Fig. 11

Prediction error and variance. a The computed RMSE for each iteration of the dual controller. b The variance measured by the controller at each iteration for the same user of Fig. 10

In Fig. 12, the packet loss threshold is 5 %. In this case, the base station has to choose a very small prediction window of 2 ms for a high mobility user with high packet loss.
Fig. 12
Fig. 12

Predicted packet loss and measurements for different prediction time windows. This figure presents the predicted and measured packet loss for various time windows for a user with bad channel conditions. The figure shows the final action taken by the controller in order to keep the packet loss below a 5 % threshold

Figure 13 a, b shows the prediction error computed at each iteration and the variance of the prediction model. As in the previous case, convergence is attained after five iterations.
Fig. 13
Fig. 13

Prediction error and variance. a The computed RMSE for each iteration of the dual controller. b The variance measured by the controller at each iteration for the same user of Fig. 12

The proposed model’s behaviour in case of a low mobility user with good channel is presented in Fig. 14 where the packet loss threshold is imposed at 30 %. In this case, the base station can choose a large prediction window of 27 ms.
Fig. 14
Fig. 14

Predicted packet loss and measurements for different prediction time windows. This figure shows the predicted and measured packet loss as function of time prediction windows for a user with very good channel conditions. The final time window chosen by the controller to keep the packet loss below the 30 % threshold is shown in the figure

Figure 15 a, b shows the prediction error committed at each iteration and the variance of the prediction model. In this case, convergence is attained after three iterations.
Fig. 15
Fig. 15

Prediction error and variance. a The computed RMSE for each iteration of the dual controller. b The variance measured by the controller at each iteration for the same user of Fig. 14

6 Conclusions

In this work, we have shown that the feedback overhead cannot be overlooked as the number of connected devices keeps increasing. Some solutions are implemented in the frequency domain to limit the impact of this signalling information on the uplink bandwidth but additional restrictions in the time domain are also necessary. We presented a GPR technique to predict the users’ channel quality for various speeds limiting the loss incurred by increasing the time sampling period. The proposed CQI prediction method is able to estimate a user’s channel with good accuracy. Furthermore, we have presented a dual-control method based on active learning, able to determine the optimal prediction window given a packet loss threshold. The same method is also able to probe the system in such a way that an optimal solution is reached while also limiting the system’s exploration by maximising the impact of the information collected. The proposed method shows gains of up to 94 % in signalling reduction if best CQI scheduler is used when compared with state of the art if the packet loss is capped to 5 %.

Declarations

Authors’ Affiliations

(1)
Interuniversity Micro-Electronics Center (IMEC) vzw, Kapeldreef-75, Leuven, B-3001, Belgium
(2)
Department of Electrical Engineering (ESAT) KU Leuven, Kasteelpark Arenberg 10, Leuven, B-3001, Belgium
(3)
Centre for Wireless Communications, University of Oulu, Oulu, 90570, Finland

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Copyright

© Chiumento et al.; licensee Springer. 2015

This is an Open Access article distributed under the terms of the Creative Commons Attribution License (http://creativecommons.org/licenses/by/2.0), which permits unrestricted use, distribution, and reproduction in any medium, provided the original work is properly credited.

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